View AD831_362390.PDF datasheet online --- IC-ON-LINE

Datasheet File OCR Text:

a
FEATURES Doubly-Balanced Mixer Low Distortion +24 dBm Third Order Intercept (IP3) +10 dBm 1 dB Compression Point Low LO Drive Required: -10 dBm Bandwidth 500 MHz RF and LO Input Bandwidths 250 MHz Differential Current IF Output DC to >200 MHz Single-Ended Voltage IF Output Single or Dual Supply Operation DC Coupled Using Dual Supplies All Ports May Be DC Coupled No Lower Frequency Limit--Operation to DC User-Programmable Power Consumption APPLICATIONS High Performance RF/IF Mixer Direct to Baseband Conversion Image-Reject Mixers I/Q Modulators and Demodulators PRODUCT DESCRIPTION
GND VN RFP RFN VN
4 5 6 7 8
Low Distortion Mixer AD831
FUNCTIONAL BLOCK DIAGRAM
IFN IFP
20
AN
3
2
VP
1
19
50
50
18 17 16 15
AP
COM VFB OUT VN BIAS
AD831
14
9
10
11
12
13
filtering. When building a quadrature-amplitude modulator or image reject mixer, the differential current outputs of two AD831s may be summed by connecting them together. An integral low noise amplifier provides a single-ended voltage output and can drive such low impedance loads as filters, 50 amplifier inputs, and A/D converters. Its small signal bandwidth exceeds 200 MHz. A single resistor connected between pins OUT and FB sets its gain. The amplifier's low dc offset allows its use in such direct-coupled applications as direct-to-baseband conversion and quadrature-amplitude demodulation. The mixer's SSB noise figure is 10.3 dB at 70 MHz using its output amplifier and optimum source impedance. Unlike passive mixers, the AD831 has no insertion loss and does not require an external diplexer or passive termination. A programmable-bias feature allows the user to reduce power consumption, with a reduction in the 1 dB compression point and third-order intercept. This permits a tradeoff between dynamic range and power consumption. For example, the AD831 may be used as a second mixer in cellular and two-way radio base stations at reduced power while still providing a substantial performance improvement over passive solutions.
PRODUCT HIGHLIGHTS
The AD831 is a low distortion, wide dynamic range, monolithic mixer for use in such applications as RF to IF down conversion in HF and VHF receivers, the second mixer in DMR base stations, direct-to-baseband conversion, quadrature modulation and demodulation, and doppler-shift detection in ultrasound imaging applications. The mixer includes an LO driver and a low-noise output amplifier and provides both user-programmable power consumption and 3rd-order intercept point. The AD831 provides a +24 dBm third-order intercept point for -10 dBm LO power, thus improving system performance and reducing system cost compared to passive mixers, by eliminating the need for a high power LO driver and its attendant shielding and isolation problems. The RF, IF, and LO ports may be dc or ac coupled when the mixer is operating from 5 V supplies or ac coupled when operating from a single supply of 9 V minimum. The mixer operates with RF and LO inputs as high as 500 MHz. The mixer's IF output is available as either a differential current output or a single-ended voltage output. The differential output is from a pair of open collectors and may be ac coupled via a transformer or capacitor to provide a 250 MHz output bandwidth. In down-conversion applications, a single capacitor connected across these outputs implements a low-pass filter to reduce harmonics directly at the mixer core, simplifying output
1. -10 dBm LO Drive for a +24 dBm Output Referred Third Order Intercept Point 2. Single-Ended Voltage Output 3. High Port-to-Port Isolation 4. No Insertion Loss 5. Single or Dual Supply Operation 6. 10.3 dB Noise Figure
REV. B
Information furnished by Analog Devices is believed to be accurate and reliable. However, no responsibility is assumed by Analog Devices for its use, nor for any infringements of patents or other rights of third parties which may result from its use. No license is granted by implication or otherwise under any patent or patent rights of Analog Devices. (c) Analog Devices, Inc., 1995 One Technology Way, P.O. Box 9106, Norwood. MA 02062-9106, U.S.A. Tel: 617/329-4700 Fax: 617/326-8703
LON
GND
VP
LOP
VP
AD831-SPECIFICATIONS
Parameter RF INPUT Bandwidth
(TA = +25 C and VS = 5 V unless otherwise noted; all values in dBm assume 50 load.)
Min Typ 400 Max Units MHz
Conditions -10 dBm Signal Level, IP3 +20 dBm 10.7 MHz IF and High Side Injection See Figure 1
1 dB Compression Point Common-Mode Range Bias Current DC Input Resistance Capacitance IF OUTPUT Bandwidth Conversion Gain Output Offset Voltage Slew Rate Output Voltage Swing Short Circuit Current LO INPUT Bandwidth Maximum Input Level Common-Mode Range Minimum Switching Level Bias Current Resistance Capacitance ISOLATION BETWEEN PORTS LO to RF LO to IF RF to IF DISTORTION AND NOISE 3rd Order Intercept 2rd Order Intercept 1 dB Compression Point Noise Figure, SSB POWER SUPPLIES Recommended Supply Range Quiescent Current1
NOTES 1 Quiescent current is programmable. Specifications subject to change without notice.
10 DC Coupled Differential or Common Mode 160 1.3 2
1 500
dBm V A k pF
Single-Ended Voltage Output, -3 dB Level = 0 dBm, R L = 100 Terminals OUT and VFB Connected DC Measurement; LO Input Switched 1 RL = 100 , Unity Gain
-40
200 0 15 300 1.4 75 400
+40
MHz dB mV V/s V mA MHz
-10 dBm Input Signal Level 10.7 MHz IF and High Side Injection -1 -1 Differential Input Signal DC Coupled Differential or Common Mode
+1 +1 200 17 500 2 70 30 45 24 62 10 10.3 14 50
V V mV p-p A pF dB dB dB dBm dBm dBm dB dB
LO = 100 MHz, RS = 50 , 10.7 MHz IF LO = 100 MHz, RS = 50 , 10.7 MHz IF RF = 100 MHz, RS = 50 , 10.7 MHz IF LO = -10 dBm, f = 100 MHz, IF = 10.7 MHz Output Referred, 100 mV LO Input Output Referred, 100 mV LO Input RL = 100 , R BIAS = Matched Input, RF = 70 MHz, IF = 10.7 MHz Matched Input, RF = 150 MHz, IF = 10.7 MHz Dual Supply Single Supply For Best 3rd Order Intercept Point Performance BIAS Pin Open Circuited 4.5 9
100
5.5 11 125
V V mA
-2-
REV. B
AD831
Supply Voltage VS . . . . . . . . . . . . . . . . . . . . . . . . . . 5.5 V Input Voltages RFHI, RFLO . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 3 V LOHI, LOLO . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 1 V Internal Power Dissipation2 . . . . . . . . . . . . . . . . . . 1200 mW Operating Temperature Range AD831A . . . . . . . . . . . . . . . . . . . . . . . . . . . -40C to +85C Storage Temperature Range . . . . . . . . . . . . -65C to +150C Lead Temperature Range (Soldering 60 sec) . . . . . . . . +300C
NOTES 1 Stresses above those listed under "Absolute Maximum Ratings" may cause permanent damage to the device. This is a stress rating only and functional operation of the device at these or any other conditions above those indicated in the operational section of this specification is not implied. Exposure to absolute maximum rating conditions for extended periods may affect device reliability. 2 Thermal Characteristics: 20-Pin PLCC Package: JA = 110C/Watt; JC = 20C/Watt. Note that the JA = 110C/W value is for the package measured while suspended in still air; mounted on a PC board, the typical value is JA = 90C/W due to the conduction provided by the AD831's package being in contact with the board, which serves as a heat sink.
ABSOLUTE MAXIMUM RATINGS 1
PIN CONFIGURATION 20-Lead PLCC
IFN IFP AN AP
18 COM 17 VFB 16 OUT 15 VN 14 BIAS 9 10 11 12 13
3 GND VN RFP RFN VN 4 5 6 7 8
2
VP
1
20 19
AD831
TOP VIEW (Not to Scale)
VP
LOP
VP
PIN DESCRIPTION
Pin 1 2 3 4 5 6 7 8 9 10 11 12 13 14 15 16 17 18 19 20
Mnemonic VP IFN AN GND VN RFP RFN VN VP LON LOP VP GND BIAS VN OUT VFB COM AP IFP
Description Positive Supply Input Mixer Current Output Amplifier Negative Input Ground Negative Supply Input RF Input RF Input Negative Supply Input Positive Supply Input Local Oscillator Input Local Oscillator Input Positive Supply Input Ground Bias Input Negative Supply Input Amplifier Output Amplifier Feedback Input Amplifier Output Common Amplifier Positive Input Mixer Current Output
ORDERING GUIDE
Model AD831AP
Temperature Range -40C to +85C
Package Description 20-Lead PLCC
Package Option P-20A
CAUTION ESD (electrostatic discharge) sensitive device. Electrostatic charges as high as 4000 V readily accumulate on the human body and test equipment and can discharge without detection. Although the AD831 features proprietary ESD protection circuitry, permanent damage may occur on devices subjected to high energy electrostatic discharges. Therefore, proper ESD precautions are recommended to avoid performance degradation or loss of functionality.
WARNING!
ESD SENSITIVE DEVICE
REV. B
-3-
GND
LON
AD831-Typical Characteristics
30
65
THIRD ORDER INTERCEPT - dBm
25
SECOND ORDER INTERCEPT - dBm
64
20
63
15
62
10
61
5
0 10
100 FREQUENCY - MHz
1000
60 10
100 FREQUENCY - MHz
1000
Figure 1. Third-Order Intercept vs. Frequency, IF Held Constant at 10.7 MHz
Figure 4. Second-Order Intercept vs. Frequency
80 70 60
90 80 70
ISOLATION - dB
50 40 30 20 10 0 10
ISOLATION - dB
60 50 40 30 20 10 0 10
100 FREQUENCY - MHz
1000
100 FREQUENCY - MHz
1000
Figure 2. IF-to-RF Isolation vs. Frequency
Figure 5. LO-to-RF Isolation vs. Frequency
60 2 x LO-to-IF 50 3 x LO-to-IF
80 3 x RF-to-IF 70 2 x RF-to-IF 60 2 x RF-to-IF 50 40 30 20 RF-to-IF RF-to-IF 3 x RF-to-IF
ISOLATION - dB
LO 30
20
10
ISOLATION - dB
40
10 0 10
0 10
100 FREQUENCY - MHz
1000
100 FREQUENCY - MHz
1000
Figure 3. LO-to-IF Isolation vs. Frequency
Figure 6. RF-to-IF Isolation vs. Frequency
-4-
REV. B
AD831
12
1.00 0.75
1dB COMPRESSION POINT - dBm
10
0.50
8
GAIN ERROR - dB
0.25 0.00 -0.25 -0.50
6
4
2
-0.75 -1.00 10
0 10
100 FREQUENCY - MHz
1000
100 FREQUENCY - MHz
1000
Figure 7. 1 dB Compression Point vs. Frequency, Gain = 1
Figure 10. Gain Error vs. Frequency, Gain = 1
12
9 8
1dB COMPRESSION POINT - dBm
1dB COMPRESSION POINT - dBm
100 FREQUENCY - MHz 1000
10
7 6 5 4 3 2 1
8
6
4
2
0 10
0 10
100 FREQUENCY - MHz
1000
Figure 8. 1 dB Compression Point vs. RF Input, Gain = 2
Figure 11. 1 dB Compression Point vs. Frequency, Gain = 4
25 MIXER OUTPUT TRANSFORMER COUPLED PER FIGURE 18
11 VS = 9V
THIRD ORDER INTERCEPT - dBm
1dB COMPRESSION POINT - dBm
22
10
19
VS = 8V 9
16 MIXER PLUS AMPLIFIER, G=1
8 LO LEVEL = -10dBm IF = 10.7MHz 7
13
10 100
150
200 250 FREQUENCY - MHz
300
350
0
100
200 300 400 FREQUENCY - MHz
500
600
Figure 9. Third-Order Intercept vs. Frequency , LO Held Constant at 241 MHz
Figure 12. Input 1 dB Compression Point vs. Frequency, Gain = 1, 9 V Single Supply
REV. B
-5-
AD831-Typical Characteristics
30
1200 1000 INPUT RESISTANCE INPUT CAPACITANCE 800 3.5 4.0
THIRD ORDER INTERCEPT - dBm
INPUT RESISTANCE - Ohms
25
VS = 8V
600
3.0
20 LO LEVEL = -10dBm IF = 10.7MHz f = 20kHz 15 0 50 100 150 200 250 300 350 FREQUENCY - MHz 400 450 500 VS = 9V
400
2.5
200
2.0
0 50
100
150 FREQUENCY - MHz
200
250
Figure 13. Input Third Order Intercept, 9 V Single Supply
Figure 15. Input Impedance vs. Frequency, ZIN = R C
62.4 62.2
SECOND ORDER INTERCEPT - dBm
18
VS = 9V
17 16
62.0 61.8 61.6 61.4 61.2 61.0 60.8 60.6 60.4 60.2 0 50 100 150 200 250 300 350 FREQUENCY - MHz 400 450 500 LO LEVEL = -10dBm IF = 10.7MHz f = 20kHz
NOISE FIGURE - dB
VS = 8V
15 14 13 12 11 10 9 8 50 100 150 FREQUENCY - MHz 200 250
Figure 14. Input Second Order Intercept, 9 V Single Supply
Figure 16. Noise Figure vs. Frequency, Matched Input
-6-
REV. B
INPUT CAPACITANCE - pF
AD831
THEORY OF OPERATION
The AD831 consists of a mixer core, a limiting amplifier, a low noise output amplifier, and a bias circuit (Figure 17). The mixer's RF input is converted into differential currents by a highly linear, Class A voltage-to-current converter, formed by transistors Q1, Q2 and resistors R1, R2. The resulting currents drive the differential pairs Q3, Q4 and Q5, Q6. The LO input is through a high gain, low noise limiting amplifier that converts the -10 dBm LO input into a square wave. This square wave drives the differential pairs Q3, Q4 and Q5, Q6 and produces a high level output at IFP and IFN--consisting of the sum and difference frequencies of the RF and LO inputs--and a series of lower level outputs caused by odd harmonics of the LO frequency mixing with the RF input. An on-chip network supplies the bias current to the RF and LO inputs when these are ac coupled; this network is disabled when the AD831 is dc coupled.
When the integral output amplifier is used, pins IFN and IFP are connected directly to pins AFN and AFP; the on-chip load resistors convert the output current into a voltage that drives the output amplifier. The ratio of these load resistors to resistors R1, R2 provides nominal unity gain (0 dB) from RF to IF. The expression for the gain, in decibels, is
4 1 G dB = 20 log 10 2 2
Equation 1
where
4 is the amplitude of the fundamental component of a square wave 1 is the conversion loss 2 is the small signal dc gain of the AD831 when the LO input 2
is driven fully positive or negative.
VP
1
50
50
AP 19 IFP 18mA TYP
20
3 2
AN IFN 18mA TYP BIAS
20
20
AO LOCAL OSCILLATOR LON 10 INPUT LOP 11 Q3 Q4 Q5 Q6 5k 50 R4 1k R5 1k 50
16
OUT
17
VFB
LIMITING AMPLIFIER Q2 Q1 5k R1 20 R2 20 CURRENT MIRROR
18
COM
RFP RF INPUT RFN
6 7
BIAS
VP BIAS
BIAS CURRENT
36 Q7 R3 26 36mA TYP 12mA TYP 27mA TYP
VN
Figure 17. Simplified Schematic Diagram
REV. B
-7-
AD831
The mixer has two open-collector outputs (differential currents) at pins IFN and IFP. These currents may be used to provide nominal unity RF-to-IF gain by connecting a center-tapped transformer (1:1 turns ratio) to pins IFN and IFP as shown in Figure 18.
IF OUTPUT
Low-Pass Filtering
MCLT4-1H VPOS IFP 20 18mA TYP
2
VP
1
IFN 18mA TYP
A simple low-pass filter may be added between the mixer and the output amplifier by shunting the internal resistive loads (an equivalent resistance of about 14 with a tolerance of 20%) with external capacitors; these attenuate the sum component in a down-conversion application (Figure 20). The corner frequency of this one-pole low-pass filter (f = (2 RCF)-1) should be placed about an octave above the difference frequency IF. Thus, for a 70 MHz IF, a -3 dB frequency of 140 MHz might be chosen, using CF = (2 x x 14 x 140 MHz)-1 82 pF, the nearest standard value.
CF = 1 1 = 89.7 f 2fR CF
1 20 19
LOP 11 LOCAL OSCILLATOR LON 10 INPUT
Q3
Q4
Q5
Q6
5k
2
CF
3
RF INPUT RFN
RFP
6 7
LIMITING AMPLIFIER Q2
R4 1k
R5 1k
Q1
4
AN 50 GND
5k
5
IFN
VP
IFP 50
AP COM
18
R1 20
R2 20
VN RFP
VFB
17
VP BIAS VN
BIAS CURRENT
Q7 R3 26 36mA TYP
6
OUT
16
7
RFN VN VP
9
AD831
Top View
VN 15
8
BIAS 14 LON
10
Figure 18. Connections for Transformer Coupling to the IF Output
Programming the Bias Current
LOP
11
VP
12
GND
13
Because the AD831's RF port is a Class-A circuit, the maximum RF input is proportional to the bias current. This bias current may be reduced by connecting a resistor from the BIAS pin to the positive supply (Figure 19). For normal operation, the BIAS pin is left unconnected. For lowest power consumption, the BIAS pin is connected directly to the positive supply. The range of adjustment is 100 mA for normal operation to 45 mA total current at minimum power consumption.
3 2 1 20 19
Figure 20. Low-Pass Filtering Using External Capacitors
Using the Output Amplifier
The AD831's output amplifier converts the mixer core's differential current output into a single-ended voltage and provides an output as high as 1 V peak into a 50 load (+10 dBm). For unity gain operation (Figure 21), the inputs AN and AP connect to the open-collector outputs of the mixer's core and OUT connects to VFB.
3 2 1 20 19
AN 50
4
IFN
VP
IFP 50
AP COM
18
AN 50
4
IFN
VP
IFP 50
AP COM
18
GND
GND
5
VN RFP
VFB
17
5
VN RFP
VFB
17
6
OUT
16
6
OUT
16
IF OUTPUT
7
RFN VN VP
9
AD831
Top View
VN 15
VPOS
7
1.33k BIAS 14
0.1F
8
RFN VN VP
9
AD831
Top View
VN 15
8
BIAS 14 LON
10
LON
10
LOP
11
VP
12
GND
13
NOTE ADDED RESISTOR
LOP
11
VP
12
GND
13
Figure 19. Programming the Quiescent Current
Figure 21. Output Amplifier Connected for Unity Gain Operation
-8-
REV. B
AD831
For gains other than unity, the amplifier's output at OUT is connected via an attenuator network to VFB; this determines the overall gain. Using resistors R1 and R2 (Figure 22), the gain setting expression is
G dB = 20 log 10 R1 + R2 R2
19 3 2 1 20 19
AN 50
4
IFN
VP
IFP 50
AP COM
18
GND
Equation 2
5
VN RFP
VFB
R2 51.1
17
6
OUT
R1 110
16
BPF RT RT
IF OUTPUT
3
2
1
20
7
AN IFN 50
4 GND
VP
IFP 50
AP COM
18
RFN
AD831
Top View
VN 15
8 VN
BIAS 14 VP LON
10
R2
5 VN
LOP
11
VFB
VP
12
GND
13
17
9
6
RFP
R1 OUT
16
IF OUTPUT
7
RFN
AD831
Top View
VN 15
Figure 23. Connections for Driving a Doubly-Terminated Bandpass Filter
8 VN
BIAS 14 VP
9
LON
10
LOP
11
VP
12
GND
13
Figure 22. Output Amplifier Feedback Connections for Increasing Gain
Driving Filters
Higher gains can be achieved, using different resistor ratios, but with concomitant reduction in the bandwidth of this amplifier (Figure 24). Note also that the Johnson noise of these gain-setting resistors, as well as that of the BPF terminating resistors, is ultimately reflected back to the mixer's input; thus they should be as small as possible, consistent with the permissible loading on the amplifier's output.
12 G=1
1dB COMPRESSION POINT - dBm
The output amplifier can be used for driving reverse-terminated loads. When driving an IF bandpass filter (BPF), for example, proper attention must be paid to providing the optimal source and load terminations so as to achieve the specified filter response. The AD831's wideband highly linear output amplifier affords an opportunity to increase the RF-to-IF gain to compensate for a filter's insertion and termination losses. Figure 23 indicates how the output amplifier's low impedance (voltage source) output can drive a doubly-terminated bandpass filter. The typical 10 dB of loss (4 dB of insertion loss and 6 dB due to the reverse-termination) be made up by the inclusion of a feedback network that increases the gain of the amplifier by 10 dB (x3.162). When constructing a feedback circuit, the signal path between OUT and VFB should be as short as possible.
10 G=2 8 G=4 6
4
2
0 10
100 FREQUENCY - MHz
1000
Figure 24. Output Amplifier 1 dB Compression Point for Gains of 1, 2, and 4 (Gains of 0 dB, 6 dB, and 12 dB, Respectively)
REV. B
-9-
AD831
APPLICATIONS
Careful component selection, circuit layout, power supply decoupling, and shielding are needed to minimize the AD831's susceptibility to interference from radio and TV stations, etc. In bench evaluation, we recommend placing all of the components in a shielded box and using feedthrough decoupling networks for the supply voltage. Circuit layout and construction are also critical, since stray capacitances and lead inductances can form resonant circuits and are a potential source of circuit peaking, oscillation, or both.
Dual-Supply Operation
Figure 25 shows the connections for dual supply operation. Supplies may be as low as 4.5 V but should be no higher than 5.5 V due to power dissipation.
The RF input to the AD831 is shown connected by an impedance matching network for an assumed source impedance of 50 . Figure 15 shows the input impedance of the AD831 plotted vs. frequency. The input circuit can be modeled as a resistance in parallel with a capacitance. The 82 pF capacitors (CF) connected from IFN and IFP to VP provide a low-pass filter with a cutoff frequency of approximately 140 MHz in downconversion applications (see the Theory of Operation section of this data sheet for more details). The LO input is connected single-ended because the limiting amplifier provides a symmetric drive to the mixer. To minimize intermodulation distortion, connect pins OUT and VFB by the shortest possible path. The connections shown are for unity-gain operation. At LO frequencies less than 100 MHz, the AD831's LO power may be as low as -20 dBm for satisfactory operation. Above 100 MHz, the specified LO power of -10 dBm must be used.
+5V 0.1F
CF CF 82pF 82pF
3
2
1
20
19
AN 50
4
IFN
VP
IFP 50
AP COM
18
GND
0.1F
5
51.1 VN RFP VFB
17
C1 RF INPUT L1
C2
-5V
6
OUT
110
16
RT BPF RT
IF OUTPUT
7
RFN
AD831
Top View
VN 15
-5V 0.1F
0.1F
8 VN
BIAS 14 NC VP
9
-5V
LON
10
LOP
11
VP
12
GND
13
+5V 0.1F
51.1
0.1F
+5V LO INPUT -10 dBm
Figure 25. Connections for 5 V Dual-Supply Operation Showing Impedance Matching Network and Gain of 2 for Driving Reverse-Terminated IF Filter
-10-
REV. B
AD831
Single Supply Operation
Figure 26 is similar to the dual supply circuit in Figure 19. Supplies may be as low as 9 V but should not be higher than 11 V due to power dissipation. As in Figure 19, both the RF and LO ports are driven single-ended and terminated.
+9V 0.1F 82pF
In single supply operation, the COM terminal is the "ground" reference for the output amplifier and must be biased to 1/2 the supply voltage, which is done by resistors R1 and R2. The OUT pin must be ac-coupled to the load.
82pF +5V
3
2
1
20
19
AN 50
4
IFN
VP
IFP 50
AP COM
18
5k 5k
R2 51.1 0.1F R1 110 RT CC
GND
5
VN RFP
VFB
17
C1 RF INPUT L1
C2
6
OUT
16
IF OUTPUT
0.1F
7
RFN
AD831
Top View
VN 15
8 VN
BIAS 14 NC VP
9
LON
10
LOP
11
VP
12
GND
13
0.1F +9V 0.1F 51.1
0.1F
0.1F
+9V
LO INPUT -10 dBm
Figure 26. Connections for +9 V Single-Supply Operation
REV. B
-11-
AD831
Connections Quadrature Demodulation
Two AD831 mixers may have their RF inputs connected in parallel and have their LO inputs driven in phase quadrature (Figure 27) to provide demodulated in-phase (I) and quadrature
(Q) outputs. The mixers' inputs may be connected in parallel and a single termination resistor used if the mixers are located in close proximity on the PC board.
+5V 0.1F CF CF
20
3
2
1
19
AN 50
4
IFN
VP
IFP 50
AP COM
18
GND
0.1F
5
VN RFP
VFB
17
-5V
6
OUT
16
DEMODULATED QUADRATURE OUTPUT -5V 0.1F
7
RFN VN VP
9
AD831
Top View
VN 15
0.1F
8
BIAS 14 NC LON
10
-5V
LOP
11
VP
12
GND
13
+5V 0.1F
51.1
0.1F
+5V LO INPUT AT 90 -10 dBm 51.1 +5V 0.1F CF
3 2 1
IF INPUT
CF
20
19
AN 50
4
IFN
VP
IFP 50
AP COM
18
GND
0.1F
5
VN RFP
VFB
17
-5V
6
OUT
16
DEMODULATED IN-PHASE OUTPUT -5V 0.1F
7
RFN VN VP
9
AD831
Top View
VN 15
0.1F
8
BIAS 14 NC LON
10
-5V
LOP
11
VP
12
GND
13
+5V 0.1F
51.1
0.1F
+5V LO INPUT AT 0 -10 dBm
Figure 27. Connections for Quadrature Demodulation
-12-
REV. B
AD831
Table I. AD831 Mixer Table, 4.5 V Supplies, LO = -9 dBm
LO Level -9.0 dBm, LO Frequency 130.7 MHz, Data File imdTB10771 RF Level 0.0 dBm, RF Frequency 120 MHz Temperature Ambient Dut Supply 4.50 V VPOS Current 90 mA VNEG Current 91 mA Intermodulation Table RF harmonics (rows) x LO harmonics (columns). First row absolute value of nRF-mLO, and second row is the sum. 0 0 1 2 3 4 5 6 7 -31.6 -31.6 -45.3 -45.3 -54.5 -54.5 -67.1 -67.1 -53.5 -53.5 -73.6 -73.6 -73.8 -73.8 1 -32.7 -32.7 0.0 -28.5 -48.2 -42.4 -57.1 -65.5 -63.1 -53.6 -62.6 -68.4 -57.7 -73.5 -73.9 -73.8 2 -35.7 -35.7 -37.2 -26.7 -39.4 -49.4 -57.5 -46.0 -69.9 -72.9 -73.8 -70.8 -68.6 -72.7 -63.4 -73.2 3 -21.1 -21.1 -41.5 -28.0 -57.6 -42.5 -50.6 -63.7 -69.9 -71.2 -72.3 -72.8 -73.1 -73.5 -72.6 -73.8 4 -11.6 -11.6 -30.4 -27.2 -44.9 -51.1 -62.6 -60.6 -69.6 -70.1 -70.7 -73.4 -73.8 -73.6 -74.6 -72.6 5 -19.2 -19.2 -34.3 -33.2 -42.4 -46.2 -55.8 -69.6 -74.1 -72.6 -71.1 -73.2 -73.0 -73.1 -74.9 -73.7 6 -35.1 -35.1 -25.2 -34.3 -40.2 -58.1 -59.7 -72.7 -69.7 -73.5 -74.3 -73.3 -72.9 -72.4 -73.6 -73.5 7 -41.9 -41.9 -40.1 -44.8 -40.2 -61.6 -55.2 -73.5 -58.6 -72.7 -73.0 -72.5 -74.4 -73.7 -74.5 -72.9
Table II. AD831 Mixer Table,
5 V Supplies, LO = -9 dBm
LO Level -9.0 dBm, LO Frequency 130.7 MHz, Data File imdTB13882 RF Level 0.0 dBm, RF Frequency 120 MHz Temperature Ambient Dut Supply 5.00 V VPOS Current 102 mA VNEG Current 102 mA Intermodulation table RF harmonics (rows) x LO harmonics (columns). First row absolute value of nRF-mLO, and second row is the sum. 0 0 1 2 3 4 5 6 7 -37.5 -37.5 -45.9 -45.9 -46.4 -46.4 -45.1 -45.1 -35.2 -35.2 -63.4 -63.4 -67.3 -67.3 1 -36.5 -36.5 0.0 -29.1 -45.2 -39.4 -53.0 -40.0 -56.0 -39.0 -45.3 -53.0 -41.1 -66.3 -65.8 -61.6 2 -46.5 -46.5 -41.2 -38.7 -47.6 -35.7 -67.0 -50.0 -48.7 -48.1 -54.1 -62.4 -53.6 -67.2 -37.8 -66.3 3 -33.0 -33.0 -41.1 -22.9 -61.5 -38.4 -43.0 -48.9 -64.6 -58.4 -54.1 -67.3 -66.5 -67.5 -54.6 -72.9 -13- 4 -17.0 -17.0 -38.5 -28.4 -53.7 -42.3 -60.9 -57.8 -53.5 -56.1 -53.7 -67.0 -58.8 -72.9 -62.5 -71.4 5 -23.0 -23.0 -29.0 -35.3 -43.5 -53.7 -47.9 -57.0 -55.7 -63.8 -57.9 -69.4 -63.3 -71.2 -71.7 -70.7 6 -34.2 -34.2 -31.7 -34.3 -41.5 -52.8 -50.7 -71.8 -53.5 -70.5 -66.6 -73.2 -61.7 -71.7 -55.2 -72.1 7 -45.6 -45.6 -47.4 -52.4 -41.8 -66.3 -41.0 -67.4 -51.1 -67.6 -64.3 -72.9 -71.4 -73.2 -57.1 -73.1
REV. B
AD831
Table III. AD831 Mixer Table, 3.5 V Supplies, LO = -20 dBm
LO Level -20.0 dBm, LO Frequency 130.7 MHz, Data File G1T1K 0771 RF Level 0.0 dBm, RF Frequency 120 MHz Temperature Ambient Dut Supply 3.50 V VPOS Current 55 mA VNEG Current 57 mA Intermodulation Table RF harmonics (rows) x LO harmonics (columns). First row absolute value of nRF-mLO, and second row is the sum. 0 0 1 2 3 4 5 6 7 -30.3 -30.3 -50.3 -50.3 -48.4 -48.4 -66.7 -66.7 -66.9 -66.9 -78.0 -78.0 -78.4 -78.4 1 -45.2 -45.2 0.0 -29.7 -49.4 -41.0 -55.7 -52.9 -59.7 -65.9 -71.5 -76.3 -69.7 -78.3 -78.5 -78.3 2 -35.7 -35.7 -33.7 -28.2 -47.4 -51.4 -58.2 -50.0 -67.2 -78.1 -73.6 -78.1 -76.7 -78.3 -76.9 -78.2 3 -16.1 -16.1 -47.9 -24.4 -49.9 -34.7 -45.0 -64.5 -62.8 -74.2 -77.6 -78.2 -78.6 -78.2 -78.7 -78.2 4 -21.6 -21.6 -37.5 -26.0 -48.8 -49.8 -57.0 -62.8 -58.2 -77.5 -70.8 -78.1 -78.8 -78.1 -79.0 -77.9 5 -22.3 -22.3 -33.8 -47.4 -38.5 -48.6 -68.4 -73.4 -71.5 -74.4 -70.2 -78.0 -75.4 -78.0 -79.1 -77.9 6 -32.0 -32.0 -32.0 -35.9 -40.7 -68.5 -55.5 -74.0 -72.9 -77.9 -75.8 -77.9 -78.1 -77.9 -78.6 -77.8 7 -36.4 -36.4 -45.2 -49.7 -51.0 -67.9 -47.7 -71.8 -63.5 -77.5 -78.1 -77.9 -79.0 -77.8 -78.9 -77.5
Table IV. AD831 Mixer Table,
5 V Supplies, 1 k
Bias Resistor, LO = -20 dBm
LO Level -20.0 dBm, LO Frequency 130.7 MHz, Data File G1T1K 3881 RF Level 0.0 dBm, RF Frequency 120 MHz Temperature Ambient Dut Supply 3.50 V VPOS Current 59 mA VNEG Current 61 mA Intermodulation table RF harmonics (rows) x LO harmonics (columns). First row absolute value of nRF-mLO, and second row is the sum. 0 0 1 2 3 4 5 6 7 -34.1 -34.1 -46.6 -46.6 -41.3 -41.3 -53.9 -53.9 -66.9 -66.9 -77.4 -77.4 -78.9 -78.9 1 -60.6 -60.6 0.0 -27.3 -48.8 -37.8 -58.8 -47.9 -52.5 -61.4 -65.8 -69.7 -73.3 -78.6 -79.0 -78.8 2 -52.3 -52.3 -35.2 -28.7 -40.1 -47.6 -59.5 -65.2 -73.7 -70.6 -76.6 -72.9 -73.8 -78.7 -77.9 -78.7 3 -16.6 -16.6 -41.8 -20.7 -52.2 -41.7 -41.8 -62.5 -68.1 -76.9 -75.2 -77.4 -78.8 -78.6 -78.0 -78.6 -14- 4 -12.8 -12.8 -29.8 -32.9 -57.9 -54.2 -61.2 -64.2 -60.3 -76.8 -65.4 -77.7 -79.2 -78.6 -79.3 -78.3 5 -26.0 -26.0 -29.1 -39.2 -38.6 -50.4 -58.1 -73.8 -71.0 -78.6 -70.0 -78.5 -73.6 -78.4 -79.5 -78.3 6 -45.0 -45.0 -35.3 -38.2 -45.8 -64.1 -57.5 -72.3 -63.4 -78.3 -73.6 -78.4 -74.9 -78.2 -79.3 -78.1 7 -38.8 -38.8 -49.0 -47.8 -47.7 -64.9 -54.0 -72.6 -62.3 -78.1 -68.7 -78.2 -79.3 -78.2 -79.3 -78.0 REV. B
AD831
HP 6632A PROGRAMMABLE POWER SUPPLY HP 8656B SYNTHESIZED SIGNAL GENERATOR HP 6632A PROGRAMMABLE POWER SUPPLY
+5V
-5V
MCL ZFSC-2-1 COMBINER HP 8656A SYNTHESIZED SIGNAL GENERATOR
AD831
PER FIGURE 25 LO
50
HP 8561E SPECTRUM ANALYZER
HP 9920 IEEE CONTROLLER HP 9121 DISK DRIVE
FLUKE 6082A SYNTHESIZED SIGNAL GENERATOR
IEEE-488 BUS
Figure 28. Third-Order Intercept Characterization Setup
HP 6632A PROGRAMMABLE POWER SUPPLY +5V MCL ZFSC-2-1 HP 8656B SYNTHESIZED SIGNAL GENERATOR RF -5V
HP 6632A PROGRAMMABLE POWER SUPPLY
AD831
PER FIGURE 25 LO
IF
50
HP 8656B SYNTHESIZED SIGNAL GENERATOR 50
50 MCL ZFSC-2-1 50 USED FOR IF TO RF, LO LO TO RF MOVE SPECTRUM ANALYZER FOR IF MEASUREMENTS
HP 8561E SPECTRUM ANALYZER
HP 8656B SYNTHESIZED SIGNAL GENERATOR
Figure 29. IF to RF Isolation Characterization Setup
REV. B
-15-
AD831
OUTLINE DIMENSIONS
Dimensions shown in inches and (mm).
20-Lead PLCC (P-20A)
0.056 (1.42) 0.042 (1.07) 19 PIN 1 IDENTIFIER TOP VIEW 18
0.025 (0.63) 0.015 (0.38)
0.048 (1.21) 0.042 (1.07) 4
3
C1879a-10-6/95
0.021 (0.53) 0.013 (0.33) 0.330 (8.38) 0.290 (7.37) 0.032 (0.81) 0.026 (0.66)
0.050 (1.27) BSC 8 9 0.020 (0.50) R
14 13 0.356 (9.04) SQ 0.350 (8.89) 0.395 (10.02) SQ 0.385 (9.78) 0.110 (2.79) 0.085 (2.16) 0.040 (1.01) 0.025 (0.64)
-16-
REV. B
PRINTED IN U.S.A.
C1879a-10-7/95
0.048 (1.21) 0.042 (1.07)
0.180 (4.57) 0.165 (4.19)

▲Up To Search▲

Price & Availability of AD831

	To Download AD831 Datasheet File
If you can't view the Datasheet, Please click here to try to view without PDF Reader .