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U211B
Phase-Control IC - Tacho Applications/Overload Limitation
Description
The integrated circuit U211B is designed as a phase-control circuit in bipolar technology with an internal frequency-voltage converter. Furthermore, it has an internal control amplifier which means it can be used for speed-regulated motor applications. It has an integrated load limitation, tacho monitoring and soft-start functions, etc. to realize sophisticated motor control systems.
Features
D Internal frequency-to-voltage converter D Externally-controlled integrated amplifier D Overload limitation with a "fold back" characteristic D Optimized soft-start function D Tacho monitoring for shorted and open loop D Automatic retriggering switchable D Triggering pulse typ. 155 mA D Voltage and current synchronization D Internal supply-voltage monitoring D Temperature reference source D Current requirement 3 mA
Block Diagram
17(16) 1(1) 5*) Automatic retriggering Output pulse 4(4) Voltage / current detector Control amplifier
11(10) + 10(9) -
6(5) 7(6) Phase control unit o = f (V12) 3(3) Supply voltage limitation Reference voltage Voltage monitoring 2(2) -V S GND
14(13) 15(14) Load limitation speed / time controlled
16(15)
controlled current sink -VRef 12(11)
Soft start
Frequencyto-voltage converter 9(8) 8(7)
Pulse-blocking tacho monitoring
18*)
13(12)
Figure 1. Block diagram (Pins in brackets refer to SO16) *) Pins 5 and 18 connected internally
Order Information
Extended Type Number U211B-x U211B-xFP U211B-xFPG3 Package DIP18 SO16 SO16 Remarks Tube Tube Taped and reeled
Rev. A4, 03-Aug-01
1 (21)
U211B
2 (21)
R13 47 k W R 31 100 kW R14 56 k W Set speed voltage R19 100 kW C 10 2.2 m F /16V 10 11 + - Figure 2. Speed control, automatic retriggering, load limiting, soft start R3 220 kW 17 R4 470 kW 1 5 Automatic retriggering Output pulse 4 Voltage / current detector Control amplifier 6 7 R10 1 kW 1 MW R 9 C9 4.7m F /16V 15 controlled current sink -V Ref 12 R11 Actual speed voltage C6 100 nF 2 MW R6 100 kW C7 10 mF /16V 22 k W R7 C8 220 nF C3 C5 1 nF 2.2 m F 16 V 13 9 8 220 nF C4 1 kW Frequencyto-voltage converter Pulse blocking tacho 18 monitoring
1N4007 18 kW 2W
D1 R1 M
L
R 12 180 W R 2 1 MW 3.3 nF C2 C1
TIC 226
VM = 230 V ~
R8 33 mW 1W 22 m F 25 V 2.2 m F
Phasecontrol unit o = f (V12 )
Supply voltage limitation Reference voltage Voltage monitoring
3
2 -V S
N
14 Load limitation speed / time controlled
GND C 11 16
Soft start
Rev. A4, 03-Aug-01
Speed sensor R5
U211B
Pin Description
Isync GND VS Output Retr VRP CP 1 2 3 4 5 6 7 18 PB/TM 17 Vsync 16 VRef 15 OVL Pin 1 2 3 4 5 6 7 8 9 10 11 12 13 14 15 16 17 18 Symbol Isync GND VS Output Retr VRP CP F/V CRV OP- OP+ CTR/OPO Csoft Isense OVL Vref Vsync PB/TM Function Current synchronization Ground Supply voltage Trigger pulse output Retrigger programming Ramp current adjust Ramp voltage Frequency-voltage converter Charge pump OP inverting input OP non-inverting input Control input / OP output Soft start Load-current sensing Overload adjust Reference voltage Voltage synchronization Pulse blocking / tacho monitoring
U211B
14 13 12 11 10
Isense Csoft CTR/OPO OP+ OP-
F/V 8 CRV 9
Figure 3. Pinning DIP18
Isync GND VS Output VRP CP F/V CRV
1 2 3 4
16 Vsync 15 VRef 14 OVL 13 Isense
U211B
5 6 7 8 12 Csoft 11 CTR/OPO 10 OP+ 9 OP-
Pin 1 2 3 4 5 6 7 8 9 10 11 12 13 14 15 16
Symbol Isync GND VS Output VRP CP F/V CRV OP- OP+ CTR/OPO Csoft Isense OVL Vref Vsync
Function Current synchronization Ground Supply voltage Trigger pulse output Ramp current adjust Ramp voltage Frequency-voltage converter Charge pump OP inverting input OP non-inverting input Control input / OP output Soft start Load-current sensing Overload adjust Reference voltage Voltage synchronization
Figure 4. Pinning SO16
Rev. A4, 03-Aug-01
3 (21)
U211B
Description
Mains Supply
The U211B is fitted with voltage limiting and can therefore be supplied directly from the mains. The supply voltage between Pin 2 (+ pol/ ) and Pin 3 builds up across D1 and R1 and is smoothed by C1. The value of the series resistance can be approximated using: R1 + VM - V S 2 IS When the potential on Pin 7 reaches the nominal value predetermined at Pin 12, then a trigger pulse is generated whose width tp is determined by the value of C2 (the value of C2 and hence the pulse width can be evaluated by assuming 8 ms/nF). At the same time, a latch is set, so that as long as the automatic retriggering has not been activated, no more pulses can be generated in that half cycle. The current sensor on Pin 1 ensures that, for operations with inductive loads, no pulse will be generated in a new half cycle as long as a current from the previous half cycle is still flowing in the opposite direction to the supply voltage at that instant. This makes sure that "gaps" in the load current are prevented. The control signal on Pin 12 can be in the range 0 V to -7 V (reference point Pin 2). If V12 = -7 V, the phase angle is at maximum = amax, i.e., the current flow angle is a minimum. The phase angle amin is minimum when V12 = V2.
Further information regarding the design of the mains supply can be found in the design hints. The reference voltage source on Pin 16 of typ. -8.9 V is derived from the supply voltage and is used for regulation. Operation using an externally stabilized DC voltage is not recommended. If the supply cannot be taken directly from the mains because the power dissipation in R1 would be too large, then the circuit shown in figure 5 should be used.
~
Voltage Monitoring
As the voltage is built up, uncontrolled output pulses are avoided by internal voltage surveillance. At the same time, all latches in the circuit (phase control, load limit regulation, soft start) are reset and the soft-start capacitor is short circuited. Used with a switching hysteresis of 300 mV, this system guarantees defined start-up behavior each time the supply voltage is switched on or after short interruptions of the mains supply.
24 V~
1 2 3 4 5
R1
C1
Soft Start
Figure 5. Supply voltage for high current requirements
Phase Control
The phase angle of the trigger pulse is derived by comparing the ramp voltage (which is mains synchronized by the voltage detector) with the set value on the control input Pin 12. The slope of the ramp is determined by C2 and its charging current. The charging current can be varied using R2 on Pin 6. The maximum phase angle amax can also be adjusted using R2.
As soon as the supply voltage builds up (t1), the integrated soft start is initiated. Figure 6 shows the behaviour of the voltage across the soft-start capacitor which is identical with the voltage on the phase-control input on Pin 12. This behavior guarantees a gentle start-up for the motor and automatically ensures the optimum run-up time.
4 (21)
Rev. A4, 03-Aug-01
U211B
VC3 V12
The converter is based on the charge pumping principle. With each negative half wave of the input signal, a quantity of charge determined by C5 is internally amplified and then integrated by C6 at the converter output on Pin 10. The conversion constant is determined by C5, its charge transfer voltage of Vch, R6 (Pin 10) and the internally adjusted charge transfer gain. Gi I10 + 8.3 I9 C5 f R6 Vch
V0
k = Gi
t1 t2 ttot t3 t
The analog output voltage is given by VO = k
Figure 6. Soft start
t1 t2 t1 + t2 t3 ttot
= build-up of supply voltage = charging of C3 to starting voltage = dead time = run-up time = total start-up time to required speed
C3 is first charged up to the starting voltage V0 with a current of typically 45 mA (t2). By then reducing the charging current to approx. 4 mA, the slope of the charging function is substantially reduced so that the rotational speed of the motor only slowly increases. The charging current then increases as the voltage across C3 increases, resulting in a progressively rising charging function which accelerates the motor more and more with increasing rotational speed. The charging function determines the acceleration up to the set-point. The charging current can have a maximum value of 55 mA.
The values of C5 and C6 must be such that for the highest possible input frequency, the maximum output voltage VO does not exceed 6 V. While C5 is charging up, the Ri on Pin 9 is approximately 6.7 kW. To obtain good linearity of the f/V converter, the time constant resulting from Ri and C5 should be considerably less (1/5) than the time span of the negative half-cycle for the highest possible input frequency. The amount of remaining ripple on the output voltage on Pin 10 is dependent on C5, C6 and the internal charge amplification. VO = Gi Vch C6 C5
The ripple Vo can be reduced by using larger values of C6. However, the increasing speed will then also be reduced. The value of this capacitor should be chosen to fit the particular control loop where it is going to be used.
Pulse Blocking
The output of pulses can be blocked by using Pin 18 (standby operation) and the system reset via the voltage monitor if V18 -1.25 V. After cycling through the switching point hysteresis, the output is released when V18 -1.5 V followed by a soft start such as that after turn-on. Monitoring of the rotation can be carried out by connecting an RC network to Pin 18. In the event of a short or open circuit, the triac triggering pulses are cut off by the time delay which is determined by R and C. The capacitor C is discharged via an internal resistance Ri = 2 kW with each charge transfer process of the f/V converter. If there are no more charge transfer processes, C is charged up via R until the switch-off threshold is exceeded and the triac triggering pulses are cut off. For operation without trigger pulse blocking or monitoring of the rotation, Pins 18 and 16 must be connected together.
Frequency-to-Voltage Converter
The internal frequency-to-voltage converter (f/Vconverter) generates a DC signal on Pin 10 which is proportional to the rotational speed using an AC signal from a tacho generator or a light beam whose frequency is in turn dependent on the rotational speed. The highimpedance input Pin 8 compares the tacho voltage to a switch-on threshold of typ. -100 mV. The switch-off threshold is given with -50 mV. The hysteresis guarantees very reliable operation even when relatively simple tacho generators are used. The tacho frequency is given by: f+ n 60 where: p (Hz)
n = revolutions per minute p = number of pulses per revolution
Rev. A4, 03-Aug-01
5 (21)
U211B
C = 1 mF 10 V 18 17 16 15 exceeds an internally set threshold of approximately 7.3 V (reference voltage Pin 16), a latch is set and the load limiting is turned on. A current source (sink) controlled by the control voltage on Pin 15 now draws current from Pin 12 and lowers the control voltage on Pin 12 so that the phase angle a is increased to amax. The simultaneous reduction of the phase angle during which current flows causes firstly: a reduction of the rotational speed of the motor which can even drop to zero if the angular momentum of the motor is excessively large, and secondly: a reduction of the potential on C9 which in turn reduces the influence of the current sink on Pin 12. The control voltage can then increase again and bring down the phase angle. This cycle of action sets up a "balanced condition" between the "current integral" on Pin 15 and the control voltage on Pin 12. Apart from the amplitude of the load current and the time during which current flows, the potential on Pin 12 and hence the rotational speed also affects the function of the load limiting. A current proportional to the potential on Pin 10 gives rise to a voltage drop across R10, via Pin 14, so that the current measured on Pin 14 is smaller than the actual current through R8. This means that higher rotational speeds and higher current amplitudes lead to the same current integral. Therefore, at higher speeds, the power dissipation must be greater than that at lower speeds before the internal threshold voltage on Pin 15 is exceeded. The effect of speed on the maximum power is determined by the resistor R10 and can therefore be adjusted to suit each individual application. If, after the load limiting has been turned on, the momentum of the load sinks below the "o-momentum" set using R10, then V15 will be reduced. V12 can then increase again so that the phase angle is reduced. A smaller phase angel corresponds to a larger momentum of the motor and hence the motor runs up - as long as this is allowed by the load momentum. For an already rotating machine, the effect of rotation on the measured "current integral" ensures that the power dissipation is able to increase with the rotational speed. The result is a current-controlled accelleration run-up which ends in a small peak of accelleraton when the set point is reached. The latch of the load limiting is simultaneously reset. The speed of the motor is then again under control and is capable of carrying its full load. The above mentioned peak of acceleration depends upon the ripple of actual speed voltage. A large amount of ripple also leads to a large peak of acceleration. The measuring resistor R8 should have a value which ensures that the amplitude of the voltage across it does not exceed 600 mV.
R = 1 MW
1
2
3
4
Figure 7. Operation delay
Control Amplifier (Figure 2)
The integrated control amplifier with differential input compares the set value (Pin 11) with the instantaneous value on Pin 10 and generates a regulating voltage on the output Pin 12 (together with the external circuitry on Pin 12) which always tries to hold the actual voltage at the value of the set voltages. The amplifier has a transmittance of typically 1000 mA/V and a bipolar current source output on Pin 12 which operates with typically 110 mA. The amplification and frequency response are determined by R7, C7, C8 and R11 (can be left out). For open-loop operation, C4, C5, R6, R7, C7, C8 and R11 can be omitted. Pin 10 should be connected with Pin 12 and Pin 8 with Pin 2. The phase angle of the triggering pulse can be adjusted using the voltage on Pin 11. An internal limitation circuit prevents the voltage on Pin 12 from becoming more negative than V16 + 1 V.
Load Limitation
The load limitation, with standard circuitry, provides absolute protection against overloading of the motor. The function of the load limiting takes account of the fact that motors operating at higher speeds can safely withstand larger power dissipations than at lower speeds due to the increased action of the cooling fan. Similarly, considerations have been made for short-term overloads for the motor which are, in practice, often required. These behavior are not damaging and can be tolerated. In each positive half-cycle, the circuit measures via R10 the load current on Pin 14 as a potential drop across R8 and produces a current proportional to the voltage on Pin 14. This current is available on Pin 15 and is integrated by C9. If, following high-current amplitudes or a large phase angle for current flow, the voltage on C9
6 (21)
Rev. A4, 03-Aug-01
U211B
Design Hints
Practical trials are normally needed for the exact determination of the values of the relevant components in the load limiting. To make this evaluation easier, the Parameters Pmax Pmin Pmax / min td tr Pmax Pmin td tr n.e R10 Increasing increases increases increases n.e. n.e. following table shows the effect of the circuitry on the important parameters of the load limiting and summarizes the general tendencies. Component R9 Increasing decreases decreases n.e. increases increases P1 = f(n) n 0 0 P1 = f(n) n = 0
C9 Increasing n.e. n.e. n.e. increases increases
- maximum continuous power dissipation - power dissipation with no rotation - operation delay time - recovery time - no effect
Pulse-Output Stage
The pulse-output stage is short-circuit protected and can typically deliver currents of 125 mA. For the design of smaller triggering currents, the function IGT = f(RGT) can be taken from figure 20.
General Hints and Explanation of Terms
To ensure safe and trouble-free operation, the following points should be taken into consideration when circuits are being constructed or in the design of printed circuit boards. - The connecting lines from C2 to Pin 7 and Pin 2 should be as short as possible. The connection to Pin 2 should not carry any additional high current such as the load current. When selecting C2, a low temperature coefficient is desirable. - The common (earth) connections of the set-point generator, the tacho generator and the final interference suppression capacitor C4 of the f/V converter should not carry load current. - The tacho generator should be mounted without influence by strong stray fields from the motor. - The connections from R10 and C5 should be as short as possible. To achieve a high noise immunity, a maximum ramp voltage of 6 V should be used. The typical resistance Ro can be calculated from Io as follows: T(ms) 1.13(V) 103 R o (kW) + C(nF) 6(V) T = Period duration for mains frequency (10 ms at 50 Hz) Co = Ramp capacitor, max. ramp voltage 6 V and constant voltage drop at Ro = 1.13 V. A 10% lower value of Ro (under worst case conditions) is recommended.
Automatic Retriggering
The variable automatic retriggering prevents half cycles without current flow, even if the triac is turned off earlier, e.g., due to a collector which is not exactly centered (brush lifter) or in the event of unsuccessful triggering. If necessary, another triggering pulse is generated after a time lapse which is determined by the repetition rate set by resistance between Pin 5 and Pin 3 (R5-3). With the maximum repetition rate (Pin 5 directly connected to Pin 3), the next attempt to trigger comes after a pause of 4.5 tp and this is repeated until either the triac fires or the half cycle finishes. If Pin 5 is not connected, then only one trigger pulse per half cycle is generated. Because the value of R5-3 determines the charging current of C2, any repetition rate set using R5-3 is only valid for a fixed value of C2.
Rev. A4, 03-Aug-01
7 (21)
U211B
V Mains Supply p/2 p 3/2p 2p
VGT Trigger Pulse VL Load Voltage
tp
tpp = 4.5 tp
IL Load Current F
o
Figure 8. Explanation of terms in phase relationship
Design Calculations for Mains Supply
The following equations can be used for the evaluation of the series resistor R1 for worst case conditions: R 1max + 0.85 VMmin - V Smax 2 I tot R 1min + VM - V Smin 2 I Smax
P (R1max) + where: VM
VS
(V Mmax - V Smin)2 2 R1
= Mains voltage = Supply voltage on Pin 3 Itot = Total DC current requirement of the circuit = IS + Ip + Ix ISmax = Current requirement of the IC in mA Ip = Average current requirement of the triggering pulse = Current requirement of other peripheral components Ix R1 can be easily evaluated from the figures 22 to 24.
8 (21)
Rev. A4, 03-Aug-01
U211B
Absolute Maximum Ratings
Reference point Pin 2, unless otherwise specified Parameters Current requirement q t 10 ms Synchronization current t t 10 ms t t 10 ms f/V converter Input current p t t 10 ms Load limiting Limiting current, negative half wave g g t t 10 ms Input voltage Phase control Input voltage Input current Soft start Input voltage Pulse output Reverse voltage Pulse blocking Input voltage Amplifier Input voltage Pin 9 open Reference voltage source Output current Storage temperature range Junction temperature Ambient temperature range Pin 14 Pin 15 Pin 12 Pin 12 Pin 6 Pin 13 Pin 4 Pin 18 Pin 11 Pin 10 Pin 16 Pin 14 II II Vi -VI -VI II -II -VI VR -VI VI -VI Io Tstg Tj Tamb 5 35 1 V16 to 0 0 to 7 500 1 V16 to 0 VS to 5 V16 to 0 0 to VS V16 to 0 7.5 -40 to +125 125 -10 to +100 mA mA V V V mA mA V V V V V mA C C C Pin 1 Pin 17 Pin 1 Pin 17 Pin 8 Pin 3 Symbol -IS -is IsyncI IsyncV iI iI II iI Value 30 100 5 5 35 35 3 13 Unit mA mA mA mA mA mA mA mA
Thermal Resistance
Junction ambient Parameters DIP18 SO16 on p.c. SO16 on ceramic Symbol RthJA RthJA RthJA Maximum 120 180 100 Unit K/W K/W K/W
Rev. A4, 03-Aug-01
9 (21)
U211B
Electrical Characteristics
-VS = 13.0 V, Tamb = 25C, reference point Pin 2, unless otherwise specified Parameters Supply voltage for mains operation Supply voltage limitation DC current requirement Reference voltage source Temperature coefficient Voltage monitoring Turn-on threshold Turn-off threshold Phase-control currents Synchronization current y Test Conditions / Pins Pin 3 -IS = 4 mA -IS = 30 mA -VS = 13.0 V -IL = 10 mA -IL = 5 mA Pin 3 Symbol -VS Min. 13.0 14.6 14.7 1.2 8.6 8.3 Typ. Max. VLimit 16.6 16.8 3.0 9.2 9.1 Unit V V V mA V V mV/K V V 2.0 2.0 1.6 1.8 mA mA V
-VS -VS Pin 3 IS Pin 16 -VRef -VRef Pin 16 -TCVRef Pin 3 Pin 3 Pin 1 -VSON -VSOFF "IsyncI "IsyncV
2.5 8.9 0.5
11.2 9.9 0.35 0.35 1.4
13.0 10.9
Voltage limitation "VI Reference ramp, see figure 9 Charge current I7 = f (R6); R6 = 50 k to 1 MW Pin 7 I7 Ro-reference voltage a 180C Pins 6 and 3 VoRef Temperature coefficient Pin 6 TCVoRef Pulse output, see figure 20 Pin 4 Output pulse current RGT = 0, VGT = 1.2 V Io Reverse current Ior Output pulse width C = 10 nF tp Amplifier Common-mode signal range Pins 10 and 11 V10, 11 Input bias current Pin 11 IIO Input offset voltage Pins 10 and 11 V10 Output current Pin 12 -IO +IO Short circuit forward, See figure 16 transmittance I12 = f(V10 -11) Pin 12 Yf Pulse blocking, tacho monitoring Pin 18 Logic-on -VTON Logic-off -VTOFF Input current V18 = VTOFF = 1.25 V II V18 = V16 II Output resistance RO
Pin 17 "IL = 5 mA Pins 1 and 17
1 1.06
20 1.13 0.5 155 0.01 80
1.18
mA V mV/K mA mA ms V mA mV mA mA mA/V V V mA mA kW
100
190 3.0
V16 0.01 10 110 120 1000 3.7 1.5 1.25 0.3 6
-1 1 145 165
75 88
1.0 1 10
14.5 1.5
10 (21)
Rev. A4, 03-Aug-01
U211B
Electrical Characteristics (continued)
-VS = 13.0 V, Tamb = 25C, reference point Pin 2, unless otherwise specified Parameters Test Conditions / Pins Symbol Frequency-to-voltage converter Pin 8 Input bias current IIB Input voltage limitation See figure 15 II = -1 mA -VI II = +1 mA +VI Turn-on threshold -VTON Turn-off threshold -VTOFF Charge amplifier Discharge current See figure 2, C5 = 1 nF, Idis Pin 9 Charge transfer voltage Pins 9 to 16 Vch Charge transfer gain I10/I9 Pins 9 and 10 Gi Conversion factor See figure 2 C5 = 1 nF, R6 = 100 kW K Output operating range Pins 10 to 16 VO Linearity Soft start, see figures 10, 12, f/v-converter non-active Starting current V13 = V16, V8 = V2 Pin 13 IO Final current V13 = 0.5 Pin 13 IO f/v-converter active, see figures 11, 13, 14 Starting current V13 = V16 Pin 13 IO Final current V13 = 0.5 IO Discharge current Restart pulse Pin 13 IO Automatic retriggering, see figure 21 Pin 5 Repetition rate R5-3 = 0 tpp R5-3 = 15 kW tpp Load limiting, see figures 17, 18, 19 Pin 14 Operating voltage range Pin 14 VI Offset current V10 = V16 Pin 14 IO V14 = V2 via 1 kW IO Pin 15-16 Input current V10 = 4.5 V Pin 14 II Output current V14 = 300 mV Pin 15-16 IO Overload ON Pin 15-16 VTON Min. Typ. 0.6 660 7.25 20 100 50 0.5 6.50 7.5 6.70 8.3 5.5 0-6
1
Max. 2 750 8.05 150
Unit mA mV V mV mV mA
6.90 9.0
V
mV/Hz V % 55 130 7 80 10 6 mA mA mA mA mA tp tp V mA mA mA mA V
20 50 2 30 0.5 3
45 85 4 55 3 4.5 20
-1.0 5 0.1 60 110 7.05 90 7.4
1.0 12 1.0 120 140 7.7
Rev. A4, 03-Aug-01
11 (21)
U211B
240 Reference Point Pin 2 200 Phase Angle a ( ) 10nF 160 4.7nF V13 ( V ) 2.2nF 6 8 10
120 80 0 0 0.2 0.4 0.6 0.8 1.0 Ro ( MW ) C o/t=1.5nF
4 2 Reference Point Pin 16 0 t=f(C3)
Figure 9. Ramp control
100
Figure 12. Soft-start voltage (f/V-converter non-active)
10
80 I 13 ( mA ) V13 ( V )
8
Reference Point Pin 16
60
6
40 20 Reference Point Pin 16 0 0 2 4 6 V13 ( V ) 8 10
4 2 0 t=f(C3)
Figure 10. Soft-start charge current (f/V-converter non-active)
100
Figure 13. Soft-start voltage (f/V-converter active)
10 8 V13 ( V )
80 Reference Point Pin 16 I 13 ( mA ) 60
Reference Point Pin 16
6 4
40 2 20 0 0 2 4 6 V13 ( V ) 8 10 0 t=f(C3) Motor Standstill ( Dead Time ) Motor in Action
Figure 11. Soft-start charge current (f/V-converter active)
Figure 14. Soft-start function
12 (21)
Rev. A4, 03-Aug-01
U211B
500 200 250 I 14-2 ( m A) 4 I 8 ( mA ) Reference Point Pin 2 0 150
100
-250
50
-500 -10
0 -8 -6 -4 -2 0 2 0 2 4 V10-16 (V) 6 8 V8 ( V )
Figure 15. f/V-converter voltage limitation
Figure 18. Load limit control f/V dependency
250
100 200 50 I 15-16 ( m A ) I 12 ( mA ) 150
0
100 50 I15=f ( VShunt ) V10=V16
-50 Reference Point for I12 = -4V -200 -100 0 100 200 300
-100
0 0 100 200 300 400 500 600 700 V10-11 ( V ) V14-2 ( mV )
-300
Figure 16. Amplifier output characteristic
200 100
Figure 19. Load current detection
150
12-16 ( m A)
80 I GT ( mA )
60
100
-I
40 20
1.4V
VGT=0.8V
50
0 0 2 4 V15-16 ( V ) 6 8
0 0 200 400 600 800 1000 RGT ( W )
Figure 17. Load limit control
Figure 20. Pulse output
Rev. A4, 03-Aug-01
13 (21)
U211B
20 6 5 15 R 5-3 ( k W ) P(R1) ( W ) 4 3 2 5 1 0 0 6 12 tpp/tp 18 24 30 0 0 10 20 R1 ( kW ) 30 40 Mains Supply 230 V
10
Figure 21. Automatic retriggering repetition rate
50 6 5 Mains Supply 230 V 4 3 2 1 0 0 4 8 Itot ( mA ) 12 16 0
Figure 23. Power dissipation of R1
40 P(R1) ( W ) R 1( kW )
Mains Supply 230 V
30
20 10 0
3
6
9
12
15
Itot ( mA )
Figure 22. Determination of R1
Figure 24. Power dissipation of R1 according to current consumption
14 (21)
Rev. A4, 03-Aug-01
U211B
Set speed voltage 2.2 m F 10 V R31 250 kW R13 47 kW R7 15 kW
100 nF
2.2 mF/ 10 V
C10
C5
680 pF
R6
C6
C4
220 nF
C7
1 MW
220 nF
13
U211B
6
2.2 mF 10 V
4.7m F 10 V
14
15
C9
4
5
16
R9 470 kW
3
17
10 kW
R14
2
GND
-VS
R2 1 MW
220 k W
2.2 m F
18 kW 1.5 W
470 kW
R3
C11
T2
R4
180 W
18
1
R12
C2 2.2 nF Co/t
12
C8
C3
7
Ro
47 kW
1N4004
D1
R1
T1
R15
BZX55
47 kW
R16
C1 N R8= 3 x 11 m W 1W
R10 2.2 k W
M
Figure 25. Speed control, automatic retriggering, load switch-off, soft start
The switch-off level at maximum load shows in principle the same speed dependency as the original version (see figure 2), but when reaching the maximum load, the motor is switched off completely.
This function is effected by the thyristor (formed by T1 and T2) which ignites when the voltage at Pin 15 reaches typ. 7.4 V (reference point Pin 16). The circuit is thereby switched in the "stand-by mode" over the release Pin 18.
Rev. A4, 03-Aug-01
230 V~
L
22 mF 25 V
Speed sensor
10
9
100 kW
R11
11
8
R5 1 kW
15 (21)
U211B
Set speed voltage 2.2 m F 10 V R31 250 k W R13 47 k W R7 15 kW
100 nF
2.2 m F 10 V /
C10
R6
C6
680 pF
C4 220 nF
C7
C5
100 kW 220 nF
1 MW
13
6
2.2 m F 10 V
4.7m F 10 V
U211B
14
15
C9
4
5
17
2
GND -VS
16
2.2 m F
C 11
3
R2 1 MW
R9 470 kW
R14 10 kW
220 k W
18 kW 1.5 W R4
470 kW
R3
180W
18
1
R12
C2 2.2 nF C o/t
12
C8
C3
7
Ro
33 kW
R15
T2
D1 1N4004
R1
T1
C1 230 V~
22 m F 25 V
Figure 26. Speed control, automatic retriggering, load switch-off, soft start
The maximum load regulation shows the principle in the same speed dependency as the original version (see figure 2). When reaching the maximum load, the control unit is turned to amax, adjustable with R2. Then only IO flows. This function is effected by the thyristor, formed by T1 and T2 which ignites as soon as the voltage at Pin 15 reaches ca. 6.8 V (reference point Pin 16). The potential
L
at Pin 15 is lifted and kept by R14 over the internally operating threshold whereby the maximum load regulation starts and adjusts the control unit constantly to amax (IO), inspite of a reduced load current. The motor shows that the circuit is still in operation in the matter of a quiet buzzing sound.
16 (21)
Rev. A4, 03-Aug-01
N
R8 = 3 x 11 mW 1W
47 kW
R16
BZX55
R10 2.2 kW
M
Speed sensor
10
9
R11
11
8
R5 1 kW
Rev. A4, 03-Aug-01 17 (21)
C11 22 nF Figure 27. Speed control, automatic retriggering, load limiting, soft start, tacho control
C9 4.7m F
C8 R9 1 M W 220 nF
68 k W
R6 C6
C10
2.2 m F 10 V
2.2 m F 10 V 1 MW L R10 1 kW D1 1N4004 220 k W R3 18 17 16 15 14 13 1 m F / 10 V
R11 C3 1.5 MW
100 nF R31 250 kW C7 Set speed voltage
2.2 m F /10 V 12 11 10 R13 47 kW
230 V~ M R1 18 kW 1.5 W R4 N 470 k W R12 220 W C1 R8 = 3 x 11 m W 1W 22 m F 25 V
U211B
R7 22 k W
1
2 GND
3 -VS
4
5 R2 1 MW
6
7
8
9 1 nF
Ro C2 2.2 nF Co/t R5 1 kW
C5
C4 220 nF
U211B
Speed sensor
U211B
18 (21)
R8 47 kW 2.2 m F 10 V C11 22 nF all diodes BYW83 220 kW R4 18 L1 M L2 R1 230 V~ 100 W R14 18 k W 1.5 W 1 R5 470 kW IGT = 50 mA 150 nF 250 V~ C1 2 GND 3 -VS 100 W R6 4 5 R2 1 MW R3 4.7 kW 6 7 8 C6 Ro C2 Co/t 3.3 nF R10 R9 220 kW C5 470 nF 100 W R17 R16 470 W 680 pF 9 D1 1N4004 17 16 15 14 13 12 11 10 C3 R7 470 kW 10 m F C8 C7 470 nF 10 V R11 16 kW R13 Set speed max R31 100 kW C4 220 nF 4.7 m F 10 V C13 R18 Set speed min
Figure 28. Speed control with reflective opto coupler CNY70 as emitter
U211B
CNY 70
C12
47 m F 25 V
1.5 k W 100 m F 10 V
1N4004
3.5 kW / 8 W R15
C10
Z3
BZX55 C9V1
Rev. A4, 03-Aug-01
ca 220 Pulses / Revolution
D2
Rev. A4, 03-Aug-01 19 (21)
C9 R9 220 k W C11 22 nF
4.7 mF 10 V 2.2 mF 10 V C3 R11
R6 82 k W
C6 470 nF
47 m F 10 V
C10 R14 Set speed min R31 220 k W
Figure 29. Speed control, max. load control with reflective opto coupler CNY70 as emitter
820 k W 10 m F
110 kW R3 R10 1.1 kW 230 V~ M R1 150 nF 250 V~ C12 100 W 10 k W 1.1 W 1 R4 220 k W IGT = 50 mA C1 2 GND 3 -VS 100 W R12 4 5 R2 1 MW 6 7 8 9 C5 Ro C2 Co /t 3.3 nF R5 2.2 k W 680 pF 10 kW R16 1 nF 18 D1 1N4004 17 16 15 14 13 12 11 10
C7 C8 470 nF
R7 16 kW
R13 Set speed max
U211B
CNY 70
1mF C13
9V R17 33 kW R18 470 W
22 mF 25 V
C4
R8= 3 x 0.1 W
U211B
U211B
The circuit is designed as a speed control based on the reflection-coupled principle with 4 periods per revolution and a max. speed of 30.000 rpm. The separation of the coupler from the rotating aperture should be about 1 mm approximately. In this experimental circuit, the power supply for the coupler was provided externally because of the relatively high current consumption. Instructions for adjusting: D In the initial adjustment of the phase-control circuit, R2 should be adjusted so that when R14 = 0 and R31 are in min. position, the motor just turns. D The speed can now be adjusted as desired by means of R31 between the limits determined by R13 and R14. D The switch-off power of the limiting-load control can be set by R9. The lower R9, the higher the switch-off power.
Package Information
Package DIP18
Dimensions in mm
4.8 max 6.4 max 0.5 min 3.3 1.64 1.44 20.32 18 10 0.58 0.48 0.36 max 9.8 8.2 23.3 max 7.77 7.47
2.54
technical drawings according to DIN specifications
1
9 5.2 4.8 3.7
Package SO16
Dimensions in mm
10.0 9.85
1.4 0.4 1.27 8.89 16 9 0.25 0.10 0.2 3.8 6.15 5.85
technical drawings according to DIN specifications
1
8
20 (21)
Rev. A4, 03-Aug-01
U211B
Ozone Depleting Substances Policy Statement
It is the policy of Atmel Germany GmbH to 1. Meet all present and future national and international statutory requirements. 2. Regularly and continuously improve the performance of our products, processes, distribution and operating systems with respect to their impact on the health and safety of our employees and the public, as well as their impact on the environment. It is particular concern to control or eliminate releases of those substances into the atmosphere which are known as ozone depleting substances (ODSs). The Montreal Protocol (1987) and its London Amendments (1990) intend to severely restrict the use of ODSs and forbid their use within the next ten years. Various national and international initiatives are pressing for an earlier ban on these substances. Atmel Germany GmbH has been able to use its policy of continuous improvements to eliminate the use of ODSs listed in the following documents. 1. Annex A, B and list of transitional substances of the Montreal Protocol and the London Amendments respectively 2. Class I and II ozone depleting substances in the Clean Air Act Amendments of 1990 by the Environmental Protection Agency (EPA) in the USA 3. Council Decision 88/540/EEC and 91/690/EEC Annex A, B and C (transitional substances) respectively. Atmel Germany GmbH can certify that our semiconductors are not manufactured with ozone depleting substances and do not contain such substances.
We reserve the right to make changes to improve technical design and may do so without further notice. Parameters can vary in different applications. All operating parameters must be validated for each customer application by the customer. Should the buyer use Atmel Wireless & Microcontrollers products for any unintended or unauthorized application, the buyer shall indemnify Atmel Wireless & Microcontrollers against all claims, costs, damages, and expenses, arising out of, directly or indirectly, any claim of personal damage, injury or death associated with such unintended or unauthorized use. Data sheets can also be retrieved from the Internet: http://www.atmel-wm.com
Atmel Germany GmbH, P.O.B. 3535, D-74025 Heilbronn, Germany Telephone: 49 (0)7131 67 2594, Fax number: 49 (0)7131 67 2423
Rev. A4, 03-Aug-01
21 (21)

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