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LT1011/LT1011A Voltage Comparator
U
Response Time vs Overdrive
500 450
16 17 19 6012 12-BIT D/A CONVERTER INPUT 0V TO 10V R4* 2.49k R6 820 PARALLEL OUTPUTS 4 5V 24 E 12 START CLOCK f = 1.4MHz
1011 TA01
FEATURES
s s s s s s s s s
DESCRIPTIO
Pin Compatible with LM111 Series Devices Guaranteed Max 0.5mV Input Offset Voltage Guaranteed Max 25nA Input Bias Current Guaranteed Max 3nA Input Offset Current Guaranteed Max 250ns Response Time Guaranteed Min 200,000 Voltage Gain 50mA Output Current Source or Sink 30V Differential Input Voltage Fully Specified for Single 5V Operation
APPLICATIO S
s s s s s s s
SAR A/D Converters Voltage-to-Frequency Converters Precision RC Oscillator Peak Detector Motor Speed Control Pulse Generator Relay/Lamp Driver
, LTC and LT are registered trademarks of Linear Technology Corporation.
The LT (R)1011 is a general purpose comparator with significantly better input characteristics than the LM111. Although pin compatible with the LM111, it offers four times lower bias current, six times lower offset voltage and five times higher voltage gain. Offset voltage drift, a previously unspecified parameter, is guaranteed at 15V/C. Additionally, the supply current is lower by a factor of two with no loss in speed. The LT1011 is several times faster than the LM111 when subjected to large overdrive conditions. It is also fully specified for DC parameters and response time when operating on a single 5V supply. These parametric improvements allow the LT1011 to be used in high accuracy (12-bit) systems without trimming. In a 12-bit A/D application, for instance, using a 2mA DAC, the offset error introduced by the LT1011 is less than 0.5LSB. The LT1011 retains all the versatile features of the LM111, including single 3V to 18V supply operation, and a floating transistor output with 50mA source/sink capability. It can drive loads referenced to ground, negative supply or positive supply, and is specified up to 50V between V - and the collector output. A differential input voltage up to the full supply voltage is allowed, even with 18V supplies, enabling the inputs to be clamped to the supplies with simple diode clamps.
TYPICAL APPLICATIO
R1 1k FULL-SCALE TRIM R2* 6.49k 15V 20 14 LM329 7V R3 6.98k 15
10s 12-Bit A/D Converter
3.9k 15V *R2 AND R4 SHOULD TC TRACK -15V 0.001F 5V R5 1k
RESPONSE TIME (ns)
13 12 11 10 9 PARALLEL OUTPUTS 5 6 7
8
7
6
5
4
8
9
16 17 18 19 20 21 D CC CP S
AM2504 SAR REGISTER S
U
U
400 350 300 250 200 150 100 50 FALLING OUTPUT RISING OUTPUT
18 3 2 1
2
+
LT1011A 7
3
-
SERIAL OUTPUT 7475 LATCH
0 0.1
1 10 OVERDRIVE (mV)
100
1011 TA02
1
LT1011/LT1011A
ABSOLUTE MAXIMUM RATINGS
Supply Voltage (Pin 8 to Pin 4) .............................. 36V Output to Negative Supply (Pin 7 to Pin 4) LT1011AC, LT1011C .......................................... 40V LT1011AI, LT1011I ............................................ 40V LT1011AM, LT1011M ........................................ 50V Ground to Negative Supply (Pin 1 to Pin 4) ............ 30V Differential Input Voltage ...................................... 36V Voltage at STROBE Pin (Pin 6 to Pin 8) .................... 5V
PACKAGE/ORDER INFORMATION
ORDER PART NUMBER
TOP VIEW V 8 GND 1 INPUT 2 INPUT 3
+ - +
7 OUTPUT 6 BALANCE/ STROBE
LT1011ACH LT1011CH LT1011AMH LT1011MH
5 BALANCE 4 V- H PACKAGE 8-LEAD TO-5 METAL CAN
TJMAX = 150C, JA = 150C/ W, JC = 45C/ W
ELECTRICAL CHARACTERISTICS
The q denotes the specifications which apply over the full operating temperature range, otherwide specifications are at TA = 25C. VS = 15V, VCM = 0V, RS = 0, V1 = -15V, output at pin 7 unless otherwise noted.
SYMBOL VOS PARAMETER Input Offset Voltage *Input Offset Voltage IOS IB *Input Offset Current Input Bias Current *Input Bias Current CONDITIONS (Note 4)
q
RS 50k (Note 5)
q
(Note 5)
q
(Note 4) (Note 5)
q
*Indicates parameters which are guaranteed for all supply voltages, including a single 5V supply. See Note 5.
2
U
U
W
WW U
W
(Note 1)
Input Voltage (Note 2) ....................... Equal to Supplies Output Short-Circuit Duration .............................. 10 sec Operating Temperature Range (Note 3) LT1011AC, LT1011C ............................... 0C to 70C LT1011AI, LT1011I ........................... - 40C to 85C LT1011AM, LT1011M ..................... - 55C to 125C Storage Temperature Range ................. - 65C to 150C Lead Temperature (Soldering, 10 sec).................. 300C
ORDER PART NUMBER
TOP VIEW GND 1 INPUT 2 INPUT 3 V- 4
+ -
8 7 6 5
V+ OUTPUT BALANCE/ STROBE BALANCE
J8 PACKAGE N8 PACKAGE 8-LEAD CERDIP 8-LEAD PDIP S8 PACKAGE 8-LEAD PLASTIC SO TJMAX = 150C, JA = 100C/ W(J8) TJMAX = 150C, JA = 130C/ W(N8) TJMAX = 150C, JA = 150C/ W(S8)
LT1011ACJ8 LT1011CJ8 LT1011ACN8 LT1011CN8 LT1011CS8 LT1011AIS8 LT1011IS8 LT1011AMJ8 LT1011MJ8 S8 PART MARKING 1011 1011AI 1011I
LT1011AC/AI/AM MIN TYP MAX 0.3 0.5 1.0 0.75 1.50 0.2 15 20 3 5 25 35 50
LT1011C/I/M MIN TYP MAX 0.6 1.5 3.0 2.0 3.0 0.2 20 25 4 6 50 65 80
UNITS mV mV mV mV nA nA nA nA nA
LT1011/LT1011A
ELECTRICAL CHARACTERISTICS
The q denotes the specifications which apply over the full operating temperature range, otherwide specifications are at TA = 25C. VS = 15V, VCM = 0V, RS = 0, V1 = -15V, output at pin 7 unless otherwise noted.
SYMBOL VOS T AVOL PARAMETER Input Offset Voltage Drift (Note 6) *Large-Signal Voltage Gain CONDITIONS TMIN T TMAX RL = 1k to 15V, -10V VOUT 14.5V RL = 500 to 5V, 0.5V VOUT 4.5V CMRR Common Mode Rejection Ratio *Input Voltage Range (Note 9) tD VOL *Response Time *Output Saturation Voltage, V1 = 0 *Output Leakage Current *Positive Supply Current *Negative Supply Current *Strobe Current (Note 8) Input Capacitance Minimum to Ensure Output Transistor is Off 500 6 VS = 15V VS = Single 5V (Note 7) VIN = 5mV, ISINK = 8mA, TJ 100C VIN = 5mV, ISINK = 8mA VIN = 5mV, ISINK = 50mA VIN = 5mV, V1 = -15V, VOUT = 35V (25V for LT1011C/I)
q q q q q q
LT1011AC/AI/AM MIN TYP MAX 4 200 50 94 -14.5 0.5 150 0.25 0.25 0.70 0.2 3.2 1.7 500 300 115 13 3 250 0.40 0.45 1.50 10 500 4.0 2.5 15
LT1011C/I/M MIN TYP MAX 4 200 50 90 -14.5 0.5 150 0.25 0.25 0.70 0.2 3.2 1.7 500 6 500 300 115 13 3 250 0.40 0.45 1.50 10 500 4.0 2.5 25
UNITS V/C V/mV V/mV dB V V ns V V V nA nA mA mA A pF
*Indicates parameters which are guaranteed for all supply voltages, including a single 5V supply. See Note 5.
Note 1: Absolute Maximum Ratings are those values beyond which the life of a device may be impaired. Note 2: Inputs may be clamped to supplies with diodes so that maximum input voltage actually exceeds supply voltage by one diode drop. See Input Protection in the Applications Information section. Note 3: TJMAX = 150C. Note 4: Output is sinking 1.5mA with VOUT = 0V. Note 5: These specifications apply for all supply voltages from a single 5V to 15V, the entire input voltage range, and for both high and low output states. The high state is ISINK 100A, VOUT (V + - 1V) and the low state is ISINK 8mA, VOUT 0.8V. Therefore, this specification defines a worst-case error band that includes effects due to common mode signals, voltage gain and output load. Note 6: Drift is calculated by dividing the offset voltage difference measured at min and max temperatures by the temperature difference. Note 7: Response time is measured with a 100mV step and 5mV overdrive. The output load is a 500 resistor tied to 5V. Time measurement is taken when the output crosses 1.4V. Note 8: Do not short the STROBE pin to ground. It should be current driven at 3mA to 5mA for the shortest strobe time. Currents as low as 500A will strobe the LT1011A if speed is not important. External leakage on the STROBE pin in excess of 0.2A when the strobe is "off" can cause offset voltage shifts. Note 9: See graph "Input Offset Voltage vs Common Mode Voltage."
3
LT1011/LT1011A TYPICAL PERFOR A CE CHARACTERISTICS
Input Bias Current
45 40 35 IB FLOWS OUT OF INPUTS 0.9 0.8 0.7
EQUIVALENT OFFSET VOLTAGE (mV)
CURRENT (nA)
25 20 15 10 5 0 - 50 - 25 0 25 50 75 100 125 150 TEMPERATURE (C)
1011 G01
CURRENT (nA)
30
Input Characteristics*
5 0 -5
INPUT CURRENT (nA) COMMON MODE VOLTAGE (V)
-10 -15 - 20 - 25 - 30 - 35 - 40 0 5 10 - 20 -15 -10 - 5 INPUT VOLTAGE (V) 15 20
-1.5 - 2.0 REFERRED TO SUPPLIES 0.4 0.3 0.2 0.1 V- - 50 - 25 0 25 50 75 100 125 150 TEMPERATURE (C)
1011 G05
OUTPUT VOLTAGE (V)
*EITHER INPUT. REMAINING INPUT GROUNDED. CURRENT FLOWS OUT OF INPUT. VS = 15V
Response Time--Collector Output
6 5 4 3 2 1 0 VS = 15V OVERDRIVE 20mV 5mV 2mV 6 5 4
15V VIN 5V 500
SATURATION VOLTAGE (V)
- +
-15V
100mV 0 0
INPUT = 100mV STEP
50 100 150 200 250 300 350 400 450 TIME (ns)
1011 G07
4
UW
1011 G04
Input Offset Current
100
Worst-Case Offset Error
LM311 (FOR COMPARISON) 10 LT1011M LT1011C 1 LT1011AM LT1011AC
0.6 0.5 0.4 0.3 0.2 0.1 0 - 50 - 25 0 25 50 75 100 125 150 TEMPERATURE (C)
1011 G01
0.1 1k 10k 100k SOURCE RESISTANCE () 1M
1011 G03
Common Mode Limits
V+ - 0.5 -1.0 POSITIVE LIMIT 40 50
Transfer Function (Gain)
TA = 25C COLLECTOR OUTPUT RL = 1k
30
20
NEGATIVE LIMIT
10
EMITTER OUTPUT RL = 600 - 0.3 0.1 0.3 - 0.1 DIFFERENTIAL INPUT VOLTAGE (mV) 0.5
0 - 0.5
1011 G06
Response Time--Collector Output
VS = 15V
VIN
Collector Output Saturation Voltage
1.0 0.9 0.8 0.7 0.6 0.5 0.4 0.3 0.2 0.1 0 0 5 10 15 20 25 30 35 40 45 50 SINK CURRENT (mA)
1011 G09
15V
5V 500
PIN 1 GROUNDED
- +
-15V
3 2 1 0
OVERDRIVE 20mV 5mV 2mV
TA = 125C TA = 25C
TA = - 55C
100mV 0 0
INPUT = 100mV STEP
50 100 150 200 250 300 350 400 450 TIME (ns)
1011 G08
LT1011/LT1011A TYPICAL PERFOR A CE CHARACTERISTICS
Response Time Using GND Pin as Output
15
INPUT VOLTAGE (mV) OUTPUT VOLTAGE (V) INPUT VOLTAGE (mV) OUTPUT VOLTAGE (V)
10 5 0 -5 -10 -15 0 - 50 -100
V+ VIN VOUT 2k V
-
10 5 0 -5 -10 -15 0 - 50 -100 0 1
VIN VOUT 2k V-
SHORT-CIRCUIT CURRENT (mA)
20mV
5mV
2mV
0
1
2 TIME (s)
Supply Current vs Supply Voltage
5
6 5
CURRENT (mA)
4 CURRENT (mA) POSITIVE SUPPLY COLLECTOR OUTPUT "LO" 3 POSITIVE AND NEGATIVE SUPPLY COLLECTOR OUTPUT "HI"
4 3 2 1
POSITIVE SUPPLY COLLECTOR OUTPUT "LO"
LEAKAGE CURRENT (A)
2
1
0
0
5
10 15 20 SUPPLY VOLTAGE (V)
Output Saturation-- Ground Output
5 REFERRED TO V +
V + TO GROUND PIN VOLTAGE (V)
+
4
2
8 LT1011 7 1 RL 4 V- VOUT
SATURATION VOLTAGE (V)
PROPAGATION DELAY (ns)
3
3
600
INPUT
TJ = - 55C TJ = 25C TJ = 125C
2
400
0.2 0.1 0
TJ = - 55C
1
200
0
0
10
30 40 20 OUTPUT CURRENT (mA)
50
1011 G16
0
1
5 6 2 3 4 INPUT OVERDRIVE (mV)
7
8
0
0
1
2
1011 G17
+
0.3
TJ = 25C
2
-
UW
VS = 15V TA = 25C 3
25
V+
Response Time Using GND Pin as Output
15
V+
Output Limiting Characteristics*
140 120 100 80 60 40 20 0 0 SHORT-CIRCUIT CURRENT TA = 25C POWER DISSIPATION 0.7 0.6
POWER DISSIPATION (W)
0.5 0.4 0.3 0.2 0.1 0
20mV
5mV
2mV VS = 15V TA = 25C
*MEASURED 3 MINUTES AFTER SHORT 10 5 OUTPUT VOLTAGE (V) 15
1011 G12
4
1011 G10
2 TIME (s)
3
4
1011 G11
Supply Current vs Temperature
10 -7
Output Leakage Current
VS = 15V
10 -8 VOUT = 35V VGND = -15V
10 -9
10 -10
POSITIVE AND NEGATIVE SUPPLY COLLECTOR OUTPUT "HI" 10 -11 50 25 75 0 TEMPERATURE (C) 100 125 25 45 65 85 TEMPERATURE (C) 105 125
1011 G15
30
1011 G13
0 -50 -25
1011 G14
Output Saturation Voltage
0.6 0.5 TJ = 125C 0.4 ISINK = 8mA
1000
Response Time vs Input Step Size
VS = 15V RL = 500 TO 5V OVERDRIVE = 5mV
5V 3 500 7 1
800
RISING INPUT FALLING INPUT
3
4567 INPUT STEP (V)
8
9
10
1011 G18
5
LT1011/LT1011A TYPICAL PERFOR A CE CHARACTERISTICS
Input Offset Voltage vs Common Mode Voltage
2.5 2.0
CHANGE IN VOS (mV/A)
TJ = 25C
INPUT OFFSET VOLTAGE (mV)
1.5 1.0 0.5 0 - 0.5 -1.0 -1.5 - 2.0 - 2.5 V - (OR GND WITH SINGLE SUPPLY) V - 0.1 0.2 0.3 0.4 0.5 0.6 0.7 COMMON MODE VOLTAGE (V) V+
1011 G19
APPLICATIONS INFORMATION
Preventing Oscillation Problems Oscillation problems in comparators are nearly always caused by stray capacitance between the output and inputs or between the output and other sensitive pins on the comparator. This is especially true with high gain bandwidth comparators like the LT1011, which are designed for fast switching with millivolt input signals. The gain bandwidth product of the LT1011 is over 10GHz. Oscillation problems tend to occur at frequencies around 5MHz, where the LT1011 has a gain of 2000. This implies that attenuation of output signals must be at least 2000:1 at 5MHz as measured at the inputs. If the source impedance is 1k, the effective stray capacitance between output and input must have a reactance of more than (2000)(1k) = 2M, or less than 0.02pF. The actual interlead capacitance between input and output pins on the LT1011 is less than 0.002pF when cut to printed circuit mount length. Additional stray capacitance due to printed circuit traces must be minimized by routing the output trace directly away from input lines and, if possible, running ground traces next to input traces to provide shielding. Additional steps to ensure oscillation-free operation are: 1. Bypass the STROBE/BALANCE pins with a 0.01F capacitor connected from Pin 5 to Pin 6. This eliminates stray capacitive feedback from the output to the BALANCE pins, which are nearly as sensitive as the inputs. 2. Bypass the negative supply (Pin 4) with a 0.1F ceramic capacitor close to the comparator. 0.1F can also be used for the positive supply (Pin 8) if the pullup load is tied to a separate supply. When the pull-up load is tied directly to Pin 8, use a 2F solid tantalum bypass capacitor. 3. Bypass any slow moving or DC input with a capacitor ( 0.01F) close to the comparator to reduce high frequency source impedance. 4. Keep resistive source impedance as low as possible. If a resistor is added in series with one input to balance source impedances for DC accuracy, bypass it with a capacitor. The low input bias current of the LT1011 usually eliminates any need for source resistance balancing. A 5k imbalance, for instance, will create only 0.25mV DC offset. 5. Use hysteresis. This consists of shifting the input offset voltage of the comparator when the output changes state. Hysteresis forces the comparator to move quickly through its linear region, eliminating oscillations by "overdriving" the comparator under all input conditions. Hysteresis may be either AC or DC. AC techniques do not shift the apparent offset voltage
6
U
W
UW
Offset Pin Characteristics
0.8 0.6 0.4 0.2 0 VOLTAGE ON PINS 5 AND 6 WITH RESPECT TO V + CHANGE IN VOS FOR CURRENT INTO PINS 5 OR 6
UPPER COMMON MODE + - (1.5V) LIMIT = V
-150mV -100mV - 50mV 0 - 50 - 25
0
25 50 75 100 125 150 TEMPERATURE (C)
1011 G20
U
U
LT1011/LT1011A
APPLICATIONS INFORMATION
INPUT OFFSET VOLTAGE (mV)
of the comparator, but require a minimum input signal slew rate to be effective. DC hysteresis works for all input slew rates, but creates a shift in offset voltage dependent on the previous condition of the input signal. The circuit shown in Figure 1 is an excellent compromise between AC and DC hysteresis.
15V
2F TANT
+
8 C1 0.003F 6 LT1011 57 1 4 -15V 0.1F
1011 F01
INPUTS
Figure 1. Comparator with Hysteresis
This circuit is especially useful for general purpose comparator applications because it does not force any signals directly back onto the input signal source. Instead, it takes advantage of the unique properties of the BALANCE pins to provide extremely fast, clean output switching even with low frequency input signals in the millivolt range. The 0.003F capacitor from Pin 6 to Pin 8 generates AC hysteresis because the voltage on the BALANCE pins shifts slightly, depending on the state of the output. Both pins move about 4mV. If one pin (6) is bypassed, AC hysteresis is created. It is only a few millivolts referred to the inputs, but is sufficient to switch the output at nearly the maximum speed of which the comparator is capable. To prevent problems from low values of input slew rate, a slight amount of DC hysteresis is also used. The sensitivity of the BALANCE pins to current is about 0.5mV input referred offset for each microampere of BALANCE pin current. The 15M resistor tied from OUTPUT to Pin 5 generates 0.5mV DC hysteresis. The combination of AC and DC hysteresis creates clean oscillation-free switching with very small input errors. Figure 2 plots input referred error versus switching frequency for the circuit as shown. Note that at low frequencies, the error is simply the DC hysteresis, while at high frequencies, an additional
+
2
-
3
R2 15M
RL
OUTPUT
U
W
U
U
8 7 6 5 4 3 2 1 0 -1 -2 1
C8 TO C6 = 0.003F
OUTPUT "LO" TO "HI" OUTPUT "HI" TO "LO" (50kHz) (5kHz) 1000
1011 F02
10 100 TIME/FREQUENCY (s)
Figure 2. Input Offset Voltage vs Time to Last Transition
error is created by the AC hysteresis. The high frequency error can be reduced by reducing CH, but lower values may not provide clean switching with very low slew rate input signals. Input Protection The inputs to the LT1011 are particularly suited to general purpose comparator applications because large differential and/or common mode voltages can be tolerated without damage to the comparator. Either or both inputs can be raised 40V above the negative supply, independent of the positive supply voltage. Internal forward biased diodes will conduct when the inputs are taken below the negative supply. In this condition, input current must be limited to 1mA. If very large (fault) input voltages must be accommodated, series resistors and clamp diodes should be used (see Figure 3).
V+
R1** INPUTS
D1
D2
R3* 300 3 R4* 300 2
- +
8 LT1011 4
R2** D3 D4
D1 TO D4: 1N4148 *MAY BE ELIMINATED FOR IFAULT 1mA **SELECT ACCORDING TO ALLOWABLE FAULT CURRENT AND POWER DISSIPATION
V-
1011 F03
Figure 3. Limiting Fault Input Currents
7
LT1011/LT1011A
APPLICATIONS INFORMATION
The input resistors should limit fault current to a reasonable value (0.1mA to 20mA). Power dissipation in the resistors must be considered for continuous faults, especially when the LT1011 supplies are off. One final caution: lightly loaded supplies may be forced to higher voltages by large fault currents flowing through D1-D4. R3 and R4 limit input current to the LT1011 to less than 1mA when the input signals are held below V -. They may be eliminated if R1 and R2 are large enough to limit fault current to less than 1mA. Input Slew Rate Limitations The response time of a comparator is typically measured with a 100mV step and a 5mV to 10mV overdrive. Unfortunately, this does not simulate many real world situations where the step size is typically much larger and overdrive can be significantly less. In the case of the LT1011, step size is important because the slew rate of internal nodes will limit response time for input step sizes larger than 1V. At 5V step size, for instance, response time increases from 150ns to 360ns. See the curve "Response Time vs Input Step Size for more detail. If response time is critical and large input signals are expected, clamp diodes across the inputs are recommended. The slew rate limitation can also affect performance when differential input voltage is low, but both inputs must slew quickly. Maximum suggested common mode slew rate is 10V/s. Strobing The LT1011 can be strobed by pulling current out of the STROBE pin. The output transistor is forced to an "off" state, giving a "hi" output at the collector (Pin 7). Currents as low as 250A will cause strobing, but at low strobe currents, strobe delay will be 200ns to 300ns. If strobe current is increased to 3mA, strobe delay drops to about 60ns. The voltage at the STROBE pin is about 150mV below V + at zero strobe current and about 2V below V + for 3mA strobe current. Do not ground the STROBE pin. It must be current driven. Figure 4 shows a typical strobe circuit. Note that there is no bypass capacitor between Pins 5 and 6. This maximizes strobe speed, but leaves the comparator more sensitive to oscillation problems for slow, low
V+ I1 0.5mA
15V 5V RL 7 1 6 4 -15 3k
1011 F04
8
U
W
U
U
- +
8 LT1011
OUTPUT
TTL OR CMOS DRIVE (5V SUPPLY)
Figure 4. Typical Strobe Circuit
level inputs. A 1pF capacitor between the output and Pin 5 will greatly reduce oscillation problems without reducing strobe speed. DC hysteresis can also be added by placing a resistor from output to Pin 5. See step 5 under "Preventing Oscillation Problems." The pin (6) used for strobing is also one of the offset adjust pins. Current flow into or out of Pin 6 must be kept very low (< 0.2A) when not strobing to prevent input offset voltage shifts. Output Transistor The LT1011 output transistor is truly floating in the sense that no current flows into or out of either the collector or emitter when the transistor is in the "off" state. The equivalent circuit is shown in Figure 5.
D1
D2
COLLECTOR (OUTPUT) Q1 R1 170 V- Q2 R2 470
OUTPUT TRANSISTOR EMITTER (GND PIN)
1011 F05
Figure 5. Output Transistor Circuitry
LT1011/LT1011A
APPLICATIONS INFORMATION
In the "off" state, I1 is switched off and both Q1 and Q2 turn off. The collector of Q2 can be now held at any voltage above V - without conducting current, including voltages above the positive supply level. Maximum voltage above V - is 50V for the LT1011M and 40V for the LT1011C/I. The emitter can be held at any voltage between V + and V - as long as it is negative with respect to the collector. In the "on" state, I1 is connected, turning on Q1 and Q2. Diodes D1 and D2 prevent deep saturation of Q2 to improve speed and also limit the drive current of Q1. The R1/R2 divider sets the saturation voltage of Q2 and provides turn-off drive. Either the collector or emitter pin can be held at a voltage between V + and V -. This allows the remaining pin to drive the load. In typical applications, the emitter is connected to V - or ground and the collector drives a load tied to V + or a separate positive supply. When the emitter is used as the output, the collector is typically tied to V + and the load is connected to ground or V -. Note that the emitter output is phase reversed with respect to the collector output so that the "+" and "-" input designations must be reversed. When the collector is tied to V +, the voltage at the emitter in the "on" state is about 2V below V + (see curves). Input Signal Range The common mode input voltage range of the LT1011 is about 300mV above the negative supply and 1.5V below the positive supply, independent of the actual supply voltages (see curve in the Typical Performance Characteristics). This is the voltage range over which the output will respond correctly when the common mode voltage is applied to one input and a higher or lower signal is applied to the remaining input. If one input is inside the common mode range and one is outside, the output will be correct. If the inputs are outside the common mode range in opposite directions, the output will still be correct. If both inputs are outside the common mode range in the same direction, the output will not respond to the differential input; it will remain unconditionally high (collector output) except at - 40 C where it is undefined.
TYPICAL APPLICATIONS
Offset Balancing
R2 3k
Driving Load Referenced to Positive Supply
V+ 3 V ++ RLOAD 7 1 4 V V OR GROUND
1011 TA05
R1 20k 5 2
V+ 6 8 7
+ -
LT1011 3
1011 TA03
V ++ CAN BE GREATER OR LESS THAN V +
U
2
W
U
U
U
Driving Load Referenced to Negative Supply
V+ 2 INPUTS* 3 8 LT1011 7 1 4 RLOAD V
- +
8 LT1011
- +
V
1011 TA06
*INPUT POLARITY IS REVERSED WHEN USING PIN 1 AS OUTPUT
9
LT1011/LT1011A
TYPICAL APPLICATIONS
Strobing
2
+
LT1011 7
INPUTS* 3 2
3
-
6 TTL STROBE 1k
1011 TA04
NOTE: DO NOT GROUND STROBE PIN
Using Clamp Diodes to Improve Frequency Response*
CURRENT MODE INPUT (DAC, ETC) 2 D1 VOLTAGE INPUT R1 GROUND OR LOW IMPEDANCE REFERENCE
1011 TA09
D2 3
*SEE CURVE, "RESPONSE TIME vs INPUT STEP SIZE"
Noise Immune 60Hz Line Sync**
5V R2 75k 2VRMS TO 25VRMS 60Hz INPUT R1* 330k 5V 3 R3 1k
- +
4
8 LT1011 7 1 R4 27k
1011 TA11
C1 0.22F
2
R6 27k 5V R5 10k
*INCREASE R1 FOR LARGER INPUT VOLTAGES **LT1011 SELF OSCILLATES AT 60Hz CAUSING IT TO "LOCK" ONTO INCOMING LINE SIGNAL
10
U
Driving Ground Referred Load
V+ 8 LT1011 7 1 4 V- L1
1011 TA07
Window Detector
V+ HIGH LIMIT 2
V ++**
- +
+
LT1011 7
RL
3
-
1
VIN 2
+
LT1011 7
OUTPUT HIGH INSIDE "WINDOW" AND LOW ABOVE HIGH LIMIT OR BELOW LOW LIMIT
*INPUT POLARITY IS REVERSED WHEN USING PIN 1 AS OUTPUT **V ++ MAY BE ANY VOLTAGE ABOVE V -. PIN 1 SWINGS TO WITHIN 2V OF V++
LOW LIMIT
3
-
1
1011 TA08
Crystal Oscillator
5V
+
LT1011 7 OUTPUT 2 85kHz 100pF 3
10k
-
+ -
1
8 LT1011 4 7
1k
50k OUT
10k
10k
1011 TA10
High Efficiency** Motor Speed Controller
15V C1 50F
+
R1 1k
Q1 2N6667 1N4002
OUTPUT 60Hz
MOTOR-TACH GLOBE 397A120-2 R2 470 15V 8 R3* 10k MOTOR TACH R5 100k C2* 0.1F R4 1k C3 0.1F R6 2k R7 1k
1011 TA12
+
7 1 LT1011
2
-
3
4 *R3/C2 DETERMINES OSCILLATION - 5V TO FREQUENCY OF CONTROLLER -15V 0V TO 10V **Q1 OPERATES IN SWITCH MODE INPUT
LT1011/LT1011A
TYPICAL APPLICATIONS
Combining Offset Adjust and Strobe
V+
5k
10k
2RH** RH* 6 20k 5 LT1011 7 *HYSTERESIS IS 0.45mV/A OF CURRENT CHANGE IN RH RL **THIS RESISTOR CAUSES HYSTERESIS TO BE CENTERED AROUND VOS
1011 TA15
5
20k 6
LT1011
1011 TA13
Direct Strobe Drive When CMOS* Logic Uses Same V + Supply as LT1011
V+ 8 ** 6 LT1011
1011 TA14
C1 0.015F 3
*NOT APPLICABLE FOR TTL LOGIC
Positive Peak Detector
15V 2k INPUT 3 8 LT1011 2 4 1M** -15V *MYLAR **SELECT FOR REQUIRED RESET TIME CONSTANT 1 7 2 10k* 10k* 15V *1% METAL FILM 10k* **TRW TYPE MTR-5/120ppm/C, 25k RS 200k C1: 0.015F = POLYSTYRENE, -120ppm/C, 1011 TA16 30ppm WESCO TYPE 32-P NOTE: COMPARATOR CONTRIBUTES 10ppm/C DRIFT FOR FREQUENCIES BELOW 10kHz LOW DRIFT AND ACCURATE FREQUENCY ARE OBTAINED BECAUSE THIS CONFIGURATION REJECTS EFFECTS DUE TO INPUT OFFSET VOLTAGE AND BIAS CURRENT OF THE COMPARATOR
+
LT1008 6 OUTPUT
10k 3
+
-
C1* 2F
100pF
8
1011 TA17
Negative Peak Detector
15V
1M**
3
- +
4
8 LT1011 7 1 10k 3
2k INPUT
2
+
C1* 2F
100pF
-15V
*MYLAR **SELECT FOR REQUIRED RESET TIME CONSTANT
+
1k
-
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Combining Offset Adjustment and Hystersis
V+
TTL OR CMOS 5V
+ + -
-
1
Low Drift R/C Oscillator
15V 2
15V 1k 7 4 74HC04 x6 BUFFERED OUTPUT
+ -
1
8 LT1011
2
-
LT1008 6 OUTPUT
+
8
1011 TA18
11
LT1011/LT1011A
TYPICAL APPLICATIONS
4-Digit (10,000 Count) A/D Converter
15V ZERO TRIM INPUT 0V TO 10V C4 0.01F R5 4.7k 2 15V 8 C5 0.01F 6 LT1011 3 R7 22 1 4 -15V 15V C1* 0.1F C2** 15pF C3 0.1F R11 6.8K 7 CLOCK 1MHz OUTPUT = 1 COUNT PER mV, f = 1MHz 5V R6 4.7K
R1 1k R2 18k
1 3 5V R3 3.9k R4 5.6k 8
LF398 7 4
25 6 D1 D2
-15V
R8 3k 15V
START 12ms
TH [CMAX (pF)][1s/pF] TL 10 * CMAX * (1s/pF) TTL OR CMOS (OPERATING ON 5V) D1 R2 R1 100k 5k R3 86.6k GAIN ADJ 5V 8 2
+
10F 3 C** D3
12
+
D2
U
D3 D4
+ -
R10 1k R9 FULL-SCALE 3.65k TRIM 2N3904
R12 6.8k C6 50pF
LM329
ALL DIODES: 1N4148 *POLYSTYRENE **NPO
1011 TA19
Capacitance to Pulse Width Converter
0.01F 6 7
+
LT1011
R5 4.7k OUTPUT 1s/pF
*PW = (R2 + R3)(C) R1 + R4 , INPUT CAPACITANCE OF R1 LT1011 IS 6pF. THIS IS AN OFFSET TERM. **TYPICAL 2 SECTIONS OF 365pF VARIABLE CAPACITOR WHEN USED AS SHAFT ANGLE INDICATION
THESE COMPONENTS MAY BE ELIMINATED IF
(
)
-
4
1
NEGATIVE SUPPLY IS AVAILABLE (-1V TO -15V)
10F
1011 TA20
LT1011/LT1011A
TYPICAL APPLICATIONS
Fast Settling* Filter
100pF
VIN 4.7k -15V 15V 0.1F 100k 2 4 OFM-1A** 1F
3
10k
0.033F 5V 100 AC INPUT 5k ZERO CROSS TRIM 2 5V 1k 7 5V 74C04 820 12k HP5082-2800 x4 RECTIFIED OUTPUT 820 74C04 - 5V 12k - 5V
1011 TA23
U
- + + -
1M 15V 2 1M 4.7k 3 1 4 7 LT1008C 8 6 OUTPUT
-15V 8 LT1011 71 5 6 15V 5k 6 51 7 8 4 -15V 15V
1011 TA21
100pF
1.5k
15V 5k THRESHOLD
LT1011
100kHz Precision Rectifier
5V
+ -
4
8 LT1011
3
1
- 5V 5V
- 5V
1k
13
LT1011/LT1011A
SCHE ATIC DIAGRA
OFFSET 5
Q6 R27 3k Q31 R5 160 R4 300
Q30 INPUT (+) 2 Q29 Q1 Q28 INPUT (-) 3 Q27 D7 D5 D6 D4
Q25
Q26
R25 1.6k
R26 1.6k
PACKAGE DESCRIPTION
0.335 - 0.370 (8.509 - 9.398) DIA 0.305 - 0.335 (7.747 - 8.509) 0.040 (1.016) MAX 0.050 (1.270) MAX GAUGE PLANE 0.010 - 0.045* (0.254 - 1.143) 0.016 - 0.021** (0.406 - 0.533) *LEAD DIAMETER IS UNCONTROLLED BETWEEN THE REFERENCE PLANE AND 0.045" BELOW THE REFERENCE PLANE 0.016 - 0.024 **FOR SOLDER DIP LEAD FINISH, LEAD DIAMETER IS (0.406 - 0.610) 0.165 - 0.185 (4.191 - 4.699) REFERENCE PLANE 0.500 - 0.750 (12.700 - 19.050)
SEATING PLANE
14
U
W
OFFSET/STROBE 6 R8 800 R1 1.3k R2 1.3k Q10 R3 300 R23 4k Q11 Q5 R6 3.2k R7 3.2k Q8 Q3 Q20 R22 200 Q9 Q19 Q4 Q2 R17 200 R20 940 Q22 R19 500 R18 275 R21 960 R14 4.8k R15 700 Q18 R16 Q24 800 Q23 Q21 Q16 R24 400 R13 4 R12 470 Q7 Q14 R10 4k R11 170 OUTPUT 7 Q15 Q12 D1 D2 Q13 R9 800 V+ 8 1 GND D3 Q17 4 V-
1011 SD
W
Dimensions in inches (millimeters) unless otherwise noted. H Package 8-Lead TO-5 Metal Can (0.230 PCD)
(LTC DWG # 05-08-1321)
0.027 - 0.045 (0.686 - 1.143) 45TYP 0.028 - 0.034 (0.711 - 0.864) PIN 1
0.230 (5.842) TYP
H8 (TO-5) 0.230 PCD 1197
0.110 - 0.160 (2.794 - 4.064) INSULATING STANDOFF
LT1011/LT1011A
PACKAGE DESCRIPTION
CORNER LEADS OPTION (4 PLCS)
0.300 BSC (0.762 BSC)
0.045 - 0.068 (1.143 - 1.727) FULL LEAD OPTION
0.008 - 0.018 (0.203 - 0.457)
0 - 15 1 0.045 - 0.068 (1.143 - 1.727) 0.014 - 0.026 (0.360 - 0.660) 0.125 3.175 0.100 0.010 MIN (2.540 0.254) 2 3 4
J8 1197
0.300 - 0.325 (7.620 - 8.255)
0.009 - 0.015 (0.229 - 0.381)
0.065 (1.651) TYP 0.125 (3.175) 0.020 MIN (0.508) MIN 0.018 0.003 (0.457 0.076)
(
+0.035 0.325 -0.015 +0.889 8.255 -0.381
)
0.100 0.010 (2.540 0.254)
*THESE DIMENSIONS DO NOT INCLUDE MOLD FLASH OR PROTRUSIONS. MOLD FLASH OR PROTRUSIONS SHALL NOT EXCEED 0.010 INCH (0.254mm)
0.010 - 0.020 x 45 (0.254 - 0.508) 0.008 - 0.010 (0.203 - 0.254) 0- 8 TYP
0.016 - 0.050 0.406 - 1.270
*DIMENSION DOES NOT INCLUDE MOLD FLASH. MOLD FLASH SHALL NOT EXCEED 0.006" (0.152mm) PER SIDE **DIMENSION DOES NOT INCLUDE INTERLEAD FLASH. INTERLEAD FLASH SHALL NOT EXCEED 0.010" (0.254mm) PER SIDE
Information furnished by Linear Technology Corporation is believed to be accurate and reliable. However, no responsibility is assumed for its use. Linear Technology Corporation makes no representation that the interconnection of its circuits as described herein will not infringe on existing patent rights.
U
Dimensions in inches (millimeters) unless otherwise noted. J8 Package 8-Lead CERDIP (Narrow 0.300, Hermetic)
(LTC DWG # 05-08-1110)
0.023 - 0.045 (0.584 - 1.143) HALF LEAD OPTION 0.200 (5.080) MAX 0.015 - 0.060 (0.381 - 1.524)
0.005 (0.127) MIN
0.405 (10.287) MAX 8 7 6 5
0.025 (0.635) RAD TYP
0.220 - 0.310 (5.588 - 7.874)
NOTE: LEAD DIMENSIONS APPLY TO SOLDER DIP/PLATE OR TIN PLATE LEADS
N8 Package 8-Lead PDIP (Narrow 0.300)
(LTC DWG # 05-08-1510)
0.045 - 0.065 (1.143 - 1.651) 0.130 0.005 (3.302 0.127) 0.400* (10.160) MAX 8 7 6 5
0.255 0.015* (6.477 0.381)
1
2
3
4
N8 1197
S8 Package 8-Lead Plastic Small Outline (Narrow 0.150)
(LTC DWG # 05-08-1610)
0.189 - 0.197* (4.801 - 5.004) 0.053 - 0.069 (1.346 - 1.752) 0.004 - 0.010 (0.101 - 0.254) 8 7 6 5
0.014 - 0.019 (0.355 - 0.483)
0.050 (1.270) TYP
0.228 - 0.244 (5.791 - 6.197)
0.150 - 0.157** (3.810 - 3.988)
SO8 0996
1
2
3
4
15
LT1011/LT1011A
TYPICAL APPLICATION
10Hz to 100kHz Voltage to Frequency Converter
R7 4.7k 15V
15V R1 4.7k C1 0.002F POLYSTYRENE 15V R2 5k FULL-SCALE R3 TRIM 8.06k C2 0.68F R17 22M 15V 3 R5 2k R6 2k R8 4.7k -15V 1.5s 4.4V -15V R11 20k Q2 ALL DIODES 1N4148 TRANSISTORS 2N3904 *USED ONLY TO GUARANTEE START-UP MAY BE INCREASED FOR BETTER 10Hz TRIM RESOLUTION R15 22k Q1* R14 1k R10 2.7k 15V R9 5k LT1009 2.5V
INPUT 0V TO 10V
15V
R16 50k 10Hz TRIM - 15V
RELATED PARTS
PART NUMBER LT1016 LT1116 LT1394 LT1671 DESCRIPTION UltraFastTM Precision Comparator 12ns Single Supply Ground-Sensing Comparator UltraFast Single Supply Comparator 60ns, Low Power Comparator COMMENTS Industry Standard 10ns Comparator Single Supply Version of the LT1016 7ns, 6mA Single Supply Comparator 450A Single Supply Comparator
UltraFast is a trademark of Linear Technology Corporation.
16
Linear Technology Corporation
1630 McCarthy Blvd., Milpitas, CA 95035-7417
(408)432-1900 q FAX: (408) 434-0507 q www.linear-tech.com
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R4 1M
LINEARITY 0.01%
- +
6
8 LT1011 7 1 4 -15V 0.002F 15V 10pF
2
TTL OUTPUT 10HZ TO 100kHz 1.5s
R12 100k
1011 TA22
+
2F
R13 620k
-15V
1011fa LT/TP 0699 2K REV A * PRINTED IN USA
(c) LINEAR TECHNOLOGY CORPORATION 1991

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